Simulation and optimization of tuneable microstrip patch antenna for fifth-generation applications based on graphene

International Journal of Electrical and Computer Engineering (IJECE)
Vol. 10, No. 5, October 2020, pp. 5546~5558
ISSN: 2088-8708, DOI: 10.11591/ijece.v10i5.pp5546-5558  5546
Journal homepage: http://ijece.iaescore.com/index.php/IJECE
Simulation and optimization of tuneable microstrip patch
antenna for fifth-generation applications based on graphene
Hamzah M. Marhoon1
, Nidal Qasem2
1,2
Department of Electronics and Communications Engineering, Al-Ahliyya Amman University, Jordan
1
Department of Computer Techniques Engineering, Al-Esraa University College, Iraq
Article Info ABSTRACT
Article history:
Received Oct 27, 2019
Revised Feb 29, 2020
Accepted Apr 29, 2020
Microstrip patch antennas (MPAs) are known largely for their versatility in
terms of feasible geometries, making them applicable in many distinct
circumstances. In this paper, a graphene-based tuneable single/array
rectangular microstrip patch antenna (MPA) utilizing an inset feed
technique designed to function in multiple frequency bands are used in
a fifth-generation (5G) wireless communications system. The tuneable
antenna is used to eliminate the difficulties caused by the narrow bandwidths
typically associated with MPAs. The graphene material has a reconfigurable
surface conductivity that can be adjusted to function at the required value,
thus allowing the required resonance frequency to be selected. The simulated
tuneable antenna comprises a copper radiating patch with four graphene
strips used for tuning purposes and is designed to cover a wide frequency
band. The proposed antenna can be tuned directly by applying a direct
current (DC) voltage to the graphene strips, resulting in a variation in
the surface impedance of the graphene strips and leading to shifts in
the resonance frequency.
Keywords:
5G
60 GHz
Graphene
Microstrip patch antenna
Tuneable antenna
Copyright © 2020 Institute of Advanced Engineering and Science.
All rights reserved.
Corresponding Author:
Nidal Qasem,
Department of Electronics and Communications Engineering, Faculty of Engineering,
Al-Ahliyya Amman University,
Zip-code (Postal Address): 19328, Amman, Jordan.
Email: Ne.qasem@ammanu.edu.jo
1. INTRODUCTION
Wireless communication technology has developed rapidly to meet the demand for high traffic
capacities in electronic devices. Fifth-generation (5G) technology utilizes higher-frequency bands in order to
provide the large information capacities needed to support multi-Gbps information rates and collect infinite
information broadcasts using the latest mobile technology [1, 2].
Millimetre-wave (mm-wave) (30 to 300 GHz) technology is currently receiving increased attention
due to increasing demands for ultra-broadband communication equipment in wireless communications.
The main problem in mm-wave communication systems is to design a small-sized antenna with a wide-band
feature that includes the entire accessible band. In addition, millimetre electronic embedded circuits
integrated with mm-wave antennas are physically compact and technologically efficient. In the mm-wave
range, using the unlicensed frequency band from 57 to 64 GHz (7 GHz bandwidth) that relies on the V-band
(50 to 70 GHz) for industrial, scientific and medical applications shows promise [3, 4].
This huge quantity of spectral space (≈7 GHz) around the 60 GHz frequency provides room for
the ultra- high-speed transfer of large quantities of information from short-range applications, such as
high-definition video transmissions and point-to-point desktop connections. The next generation of wireless
technologies is expected to face spectrum scarcity in the frequency band below 10 GHz, due to the exploding
number of products, and data-intensive applications running on today’s consumer electronic products.

Int J Elec & Comp Eng ISSN: 2088-8708 
Simulation and optimization of tuneable microstrip patch antenna ... (Hamzah M. Marhoon)
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Hence, wireless communications at 60 GHz have attracted growing interest for short-range, high-data-rate
applications recently. It is an alternative range, and many applications operate within this range, such as
wireless uncompressed HD streaming, Wi-Fi, fast transfers of huge files, high-resolution radars, and personal
networks [5, 6].
The tuneable antenna is designed in such a way that resonant frequency, operational bandwidth,
radiation pattern and/or polarization can be changed manually or automatically (via software) to adapt to
different services, system requirements and the environment. These procedures are generally performed using
micro or nano electromechanical systems, microcontrollers, electrical Radio Frequency (RF) switches such as
metal semiconductor field effect transistors, diode-based technologies such as P-type N-type insulator diodes,
varactors or tuneable materials [7]. Alternatively, graphene's tuneable surface impedance can also be put to
use in reconfigurable antennas. Graphene, a combined carbon sheet arranged in a hexagonal lattice in two
dimensionals (2Ds), allows multifunctionality in terms of signal emission, transmission, modulation,
and detection, and features broadband, high speed, compact size, and particularly low loss [8, 9].
Graphene material can be used in a tuneable antenna in such a manner that the conductivity of
the surface is changed by applying an external electrical field to the graphene sheet. The graphene admittance
is adjusted by applying a Direct Current (DC) voltage bias between the graphene sheet and the ground in
such a way that the ON and OFF states become high and low impedance, respectively, as illustrated in
Figure 1. This effect is used to vary the electrical dimension of the antennas and thus change the resonant
frequency as desired. However, graphene is not limited to being an alternative to a conventional RF switch;
it can also be used to make the radiating antenna itself. Graphene tuneable antennas have been mostly studied
in the infrared and terahertz frequencies, as graphene can significantly reduce the size of the antenna and
provide high antenna reconfigurability [10, 11].
Figure 1. Graphene-based tuneable antenna
In this work, the proposed design of the tuneable single rectangular Microstrip Patch Antenna
(MPA) and tuneable rectangular Microstrip Patch Array Antenna (MPAA) provides a sufficient
reconfigurability range to compensate for the narrow bandwidth of Microstrip Patch Antennas (MPAs).
Since mm-wave antennas made entirely of graphene are expected to have low antenna efficiencies and small
reconfigurability ranges, the proposed design of the tuneable single rectangular MPA and rectangular MPAA
here uses a hybrid of copper and graphene to achieve reasonable antenna efficiency and antenna gain and an
acceptable tuneable frequency range. The organization of the paper can be summarized as follows: Section 2
provides a brief description of the rectangular MPA structure. Section 3 illustrates the simulation of
the antenna by using the MATLAB software to obtain antenna dimensions and the Computer Simulation
Technology (CST) Microwave Studio (MWS) to simulate a single rectangular MPA. Section 4 illustrates
the simulation and modeling procedure of the proposed design of graphene-based tuneable single rectangular
MPA. Section 5 illustrates the simulation procedure of the proposed design of graphene-based tuneable
rectangular MPAA. Section 6 illustrates the discussion of the obtained results from the time domain solver of
the CST-MWS after the completion of the design of the tuneable single rectangular MPA and the tuneable
rectangular MPAA. Finally, Section 7 illustrates concludes of this paper.
2. RECTANGULAR MPA
The basic construction of the single rectangular MPA is illustrated in Figure 2. The rectangular
MPA consists of a radiating patch with length (𝐿), width (𝑊), transmission line, and ground plane where are
typically made from copper. The radiating patch and the transmission line sit on top of a substrate with
thickness (ℎ) and permittivity (𝜀 𝑟) [12].

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Figure 2. Dimensions of the single rectangular MPA and feed line
3. ANTENNA DESIGN AND MODELING
In this paper, a tuneable single rectangular MPA and rectangular MPAA based on hybrid of copper
and graphene material are simulated and optimized for 5G applications. Table 1 sets the essential parameters
for designing a single rectangular MPA. In this work, the inset feeding technique is used to obtain the best
impedance between the antenna and the source of the electrical wave, where the input impedance of
the rectangular MPA inset-feed depends on the feed inset (𝑓𝑖) and, to some extent, the gap feed line spacing
(𝐺 𝑝𝑓). The resonant frequency shifts with the variation in 𝐺 𝑝𝑓, and the return loss of the antenna changes with
the variation in 𝑓𝑖 [13]. The ground plane, substrate, patch, and feed line dimensions of the simulated antenna
are summarized in Table 2, which has been produced with the help of MATLAB software and the following
equations [14, 15].
Table 1. Essential antenna parameters
Parameter Value
Operating frequency (𝑓𝑟) 60 GHz
Substrate dielectric constant (𝜀 𝑟) 2.1
Substrate height (h) 0.1 mm
Input impedance 𝑅𝑖𝑛 50 Ω
𝑊 =
𝑐
2𝑓𝑟√
(𝜀 𝑟+1)
2
(1)
𝜀 𝑟𝑒𝑓𝑓 =
𝜀 𝑟+1
2
+
𝜀 𝑟−1
2
[1 + 12
ℎ
𝑊
]
−1
2
(2)
∆𝐿 = 0.412ℎ
(𝜀 𝑟𝑒𝑓𝑓+0.3)[
𝑊
ℎ
+0.264]
(𝜀 𝑟𝑒𝑓𝑓−0.258)[
𝑊
ℎ
+0.8]
(3)
𝐿 𝑒𝑓𝑓=
𝑐
2𝑓𝑟√ 𝜀 𝑟𝑒𝑓𝑓
(4)
𝐿 = 𝐿 𝑒𝑓𝑓 − 2∆𝐿 (5)
𝑓𝑖 =
cos−1(√
𝑍 𝑜
𝑅 𝑖𝑛
)
𝜋
𝐿
(6)
𝐵 =
377𝜋
2𝑍0√ 𝜀 𝑟
(7)
𝑊𝑓 =
2ℎ
𝜋
{𝐵 − 1 − ln(2𝐵 − 1) +
𝜀 𝑟−1
2𝜀 𝑟
[ln(𝐵 − 1) + 0.39 − (
0.61
𝜀 𝑟
)]} (8)
𝐿𝑓 = 3.96 × 𝑊𝑓 (9)

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𝐺 𝑝𝑓 =
𝑐×4.65×10−9
𝑓𝑟√2𝜀 𝑟𝑒𝑓𝑓
(10)
𝑊𝑠 = 2 × 𝑊 (11)
𝐿 𝑠 = 2 × 𝐿, (12)
Where 𝜀 𝑟𝑒𝑓𝑓 is the effective dielectric constant, 𝜀 𝑟 is the dielectric constant of the substrate, ℎ is
the height of the dielectric substrate, 𝑊 is the width of the patch, 𝐿 𝑒𝑓𝑓 is the effective length, 𝐿 is the actual
patch length, ∆𝐿 is the length’s extension, 𝑍 𝑜 is equivalent to the feed line impedance, 𝑅𝑖𝑛 is the resonant
input resistance when the patch is fed at the radiating edge, 𝑊𝑓 is the feed line width, 𝐿 𝑓 is the feed line
length, 𝑊𝑠 is the width of the substrate, and 𝐿 𝑠 is the length of the substrate.
Table 2. Calculated antenna parameters
Parameter Value (mm)
Patch width (W) 2.008
Patch length (L) 1.6681
Substrate width (𝑊𝑆) 4.016
Substrate length (𝐿 𝑆) 3.3362
Feed line inset (𝑓𝑖) 0.58217
Feed line width (𝑊𝑓) 0.308
Feed line length (𝐿 𝑓) 1.21968
Patch feed line spacing (𝐺 𝑝𝑓) 0.0179
Once the parameter calculations are completed via the previous equations, the antenna simulation
process is started via the CST-MWS. Figure 3 illustrates the single rectangular MPA inside the CST-MWS.
In this work, the main aims of the optimization process are to enhance the overall antenna performance and
facilitates the antenna manufacturing process (the laser machine accuracy in manufacturing antennas is
0.08 mm [16]). Therefore, the optimization procedures for the antenna involve maximizing some parameters
and minimize some others by trial and error until the best results are reached. Table 3 summarizes
the optimized parameters for a single rectangular MPA.
Figure 3. Simulated single rectangular MPA inside the CST-MWS
Table 3. Parameter values achieved through the optimization process
Parameter Optimized Value (mm)
Patch width (W) 2
Patch length (L) 1.615
Substrate width (𝑊𝑆) 4
Substrate length (𝐿 𝑆) 3.23
Feed line inset (𝑓𝑖) 0.5
Feed line width (𝑊𝑓) 0.09
Feed line length (𝐿 𝑓) 1.8
Patch feed line spacing (𝐺 𝑝𝑓) 0.09

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4. GRAPHENE-BASED TUNEABLE SINGLE RECTANGULAR MPA
In order to demonstrate the use of graphene in a frequency reconfigurable antenna, the main design
studied is a rectangular hybrid MPA with a copper radiating patch with four graphene strips inserted inside it.
The first step of the design process is to choose the graphene strips’ locations within the antenna’s radiating
patch by monitoring the surface current distribution and select the locations of the reasonable current density.
The current density at the resonant frequency shows a greater amount of accumulated current on the radiating
patch, as illustrated in Figure 4.
Figure 4. The surface current of the antenna at the resonance frequency
The graphene strips act as a control switch to divert the current flow along with the radiating patch
of the antenna so that the effective length is larger or shorter than the physical length in the OFF or ON state,
respectively. The ON state signifies low graphene impedance (i.e. allows the current to flow through
the strip), and the OFF state signifies high graphene impedance (i.e. prevents the flow of the current through
the strip). The DC bias voltage (𝑉𝐵) can be applied directly through the feed port if the same value of 𝑉𝐵 is
desired for all graphene strips, allowing them all to be activated/deactivated at the same time. Alternatively,
a thin gap can be inserted between the radiating patch and the graphene strips to avoid a common DC bias
voltage across the antenna and allows each graphene strip to be activated and deactivated individually.
As a result, different DC bias voltages (i.e. 𝑉𝐵1 and 𝑉𝐵2) can be applied to each of the graphene strips using
individual DC bias lines [17]. In this work, the graphene strips are surrounded by copper. Hence,
that separate coaxial ports are required to apply a different value of 𝑉𝐵 to each graphene strip. Here, the first
approach in the antenna design is to use same 𝑉𝐵 for all graphene strips. In order to achieve practical values
for the ON and OFF surface impedances (𝑍𝑠 𝑂𝑁
and 𝑍𝑠 𝑂𝐹𝐹
), the following equations are used [18-20].
𝑛 =
𝜀 𝑜 𝜀 𝑟 𝑉 𝑏
𝑑𝑞
(13)
𝜇 𝑐 = ℏ𝑣𝑓√ 𝑛𝜋 (14)
𝜏 𝑠 =
4ℏ2 𝜌 𝑚 𝑣 𝑝ℎ
2 𝑣 𝑓
√𝑛𝜋𝑘 𝐵 𝑇 𝐷2 (15)
𝜏𝑙 =
𝜇 𝑙 ℏ√𝑛𝜋
𝑞 𝑣 𝑓
(16)
𝑍𝑠 =
𝑗𝜋ℏ2(2𝜋𝑓𝑟(𝜏 𝑙 𝜏 𝑠)−𝑗(𝜏 𝑙+𝜏 𝑠))
𝑞2(𝜏 𝑙 𝜏 𝑠)[𝜇 𝑐+2𝑘 𝐵 𝑇𝑙𝑛(𝑒
−
𝜇 𝑐
𝑘 𝐵 𝑇+1)]
, (17)
Where 𝜏𝑙 is the scattering effect, 𝜏 𝑠 is the relaxation time, 𝜇𝑙 represents the electron mobility
(𝑚2
/𝑉𝑠), 𝜌 𝑚 = 7.6 × 10−7
is the 2D mass density of graphene in (𝐾𝑔/𝑚2
), 𝑣 𝑝ℎ = 2.1 × 104
is the sound
velocity of longitudinal acoustic phonons in graphene (𝑚/𝑠), 𝑇 is the temperature in degrees Kelvin, ℏ is
the reduced Planck’s constant, 𝑘 𝐵 is the Boltzmann constant, 𝑞 is the electron charge (C), 𝜇 𝑐 is the graphene

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chemical potential (Ev), 𝑣𝑓 = 1 × 106
is the Fermi velocity (𝑚/𝑠), 𝑛 is the carrier density (m-2
), 𝑑 is
the graphene thickness (m), and 𝐷 is the deformation potential (𝑒𝑉). Based on the previous studies, a 𝐷 of
around ~18 𝑒𝑉 appears to be a prevalent and recognized value for graphene over a substrate [17]. The value
of the 𝑍𝑠 𝑂𝑁
/𝑍𝑠 𝑂𝐹𝐹
are determined by increasing/decreasing the density of the charge carriers in (16). Table 4
summarizes the selected parameter values of the graphene surface impedance in both ON and OFF states.
In this work, different values of the applied 𝑉𝐵 are investigated to study the effects of
increasing/decreasing the 𝑉𝐵 on the tuning of the resonance operating frequency band. While the resulting 𝑉𝐵
values may be too large to be implemented in low-power applications, such as mobile phones, future values
can be decreased by using a thin dielectric with greater 𝜀 𝑟, depending on the required application and
operating frequency band. Graphene strips are simulated via CST-MWS as ohmic sheet surface impedances.
Figure 5 illustrates the simulated antenna inside the CST-MWS, and Table 5 summarizes the graphene
strip dimensions.
Table 4. Selected parameter values for the graphene surface impedance
Parameter Value
State ON OFF
𝜇𝑙(m2
/Vs). 2.7 2.7
D (eV) 4 4
T (K) 295 295
𝑉𝐵 (V) 1 5 20 30 40 0.5
n (m-2
) 1.16×1016
5.8×1016
2.32×1017
3.48×1017
4.64×1017
6×1014
𝑍𝑆(Ω/ ) 200+25.5i 27.72 + 9.256i 11.41 + 5.7i 8+ 4.65i 6.43 + 4i 2569.6+74.7i
Figure 5. Simulated hybrid graphene and copper tuneable single rectangular MPA
Table 5. Graphene strip dimensions
Strip Dimensions Strip Dimensions
𝑆1 0.24×0.3 mm 𝑆2 0.5×0.09 mm
𝑆3 0.5×0.09 mm 𝑆4 0.25×0.3 mm
𝐷1 0.26 mm 𝐷2 0.76 mm
𝐷3 0.26 mm 𝐷4 0.20 mm
𝐷5 0.65 mm 𝐷6 0.61 mm
𝐷7 0.61 mm 𝐷8 0.60 mm
5. GRAPHENE-BASED TUNEABLE RECTANGULAR MICROSTRIP PATCH ARRAY
ANTENNA
Rectangular MPAs can be used in the form of a single antenna configuration or in a configuration of
array elements. By using antenna arrays in communication systems, the antenna performance will be
enhanced in terms of, for instance, gain, directivity and other functions that are difficult to achieve with
a single rectangular MPA [21, 22]. The simulated array is fed via a corporate feed to obtain the best
performance, as illustrated in Figure 6. This technique exerts more control over the feed for each element and
is perfect for scanning phased and multiband arrays. Therefore, it improves directivity as well as radiation
efficiency and reduces beam variations over the frequency band compared to the series feed array. In this
work, a 4×1 array antenna is used to enhance the tuneable antenna gain, directivity, efficiency and other

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parameters. The antenna element spacing plays a key role in the design process. Too large a spacing results in
the presence of grating lobes that are, in most cases, undesirable. In contrast, too small a spacing leads to
a wider beam width, which may not be acceptable. Smaller spacing also reduces the amount of space on
the feed network. The space between the elements should, therefore, be adjusted correctly, i.e. the element
spacing should be set to 0.5 λ in order to eliminate the impact of adjacent components [23]. Table 6
summarizes the corporate feed parameters before and after the optimization process. After the completion of
the corporate feed design, the previous design of the tuneable single rectangular MPA is directly coupled
with the corporate feed configuration to construct the tuneable rectangular MPAA, as illustrated in Figure 7.
Figure 6. Corporate feed for a 4×1 rectangular MPAA
Table 6. Corporate feed parameters before and after the optimization process
Parameter Calculated Optimized
Patch feed line width 0.1 mm 0.1 mm
Patch feed line length 1.84 mm 1.72 mm
Matching line left-1 width 0.17 mm 0.16mm
Matching line left-1 length 0.93 mm 0.91mm
Matching line left-2 width 0.19 mm 0.18 mm
Matching line left-2 length 0.94 mm 0.92 mm
Matching line right-1 width 0.17 mm 0.16mm
Matching line right-1 length 0.93 mm 0.91mm
Matching line right-2 width 0.19 mm 0.18 mm
Matching line right-2 length 0.94 mm 0.92 mm
Feed line width 0.1 mm 0.1 mm
Feed line length 8.19 mm 8.18 mm
Figure 7. 4×1 tuneable rectangular MPAA inside the CST-MWS
6. RESULTS AND DISCUSSION
In this part, the results obtained after the antenna simulation is completed within the CST-MWS
simulation software will be illustrated. The simulated return loss (𝑆11) of the single rectangular MPA in
the ON/OFF states from the time domain solver of the CST-MWS is illustrated in Figure 8. Generally,
the MPAs have poor gain due to the antenna gain being affected by the substrate thickness and relative
dielectric constant. The antenna gain is inversely proportional to 𝜀 𝑟 and directly proportional to substrate
thickness [24]. Figure 9 shows the Three-Dimensional (3D) results of the far field of the proposed tuneable
single rectangular MPA at the operating frequencies 𝑓𝑟= 56.329, 56.724, 59.043, 59.743, 59.901 and 60 GHz.
The proposed antenna has a reasonable gain in the frequency range 56.3295-60 GHz.

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The radiation pattern of the single rectangular MPA is characterized by a single main lobe of
moderate beam width. Often, the beam width in the azimuth and elevation planes are similar, resulting in
a fairly circular beam, although this is by no means universal [25]. The beam widths can be manipulated to
produce an antenna with higher or lower gain, depending on the required application. The 3 dB beam widths
of the proposed antenna at different previous resonance frequencies are illustrated in Figure 10.
Figure 8. Return loss vs frequency of the tuneable single rectangular MPA for different values of 𝑉𝐵
(a) (b)
(c) d)
(e) (f)
Figure 9. Gain of the tuneable single rectangular MPA, (a) 𝑓𝑟 56.329 GHz, (b) 𝑓𝑟 56.724 GHz,
(c) 𝑓𝑟 59.043 GHz, (d) 𝑓𝑟 59.743 GHz, (e) 𝑓𝑟 59.901 GHz, (f) 𝑓𝑟 60 GHz

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(a) (b)
(c) (d)
(e) (f)
Figure 10. Radiation pattern of the tuneable single rectangular MPA, (c) 𝑓𝑟 59.043 GHz, (d) 𝑓𝑟 59.743
GHz, (e) 𝑓𝑟 59.901 GHz, (f) 𝑓𝑟 60 GHz
The bandwidth of the antenna can be calculated from the return loss plot, the simulation results for
the proposed tuneable single rectangular MPA bandwidth at 𝑆11-10 dB are summarized in Table 7.
The simulated return losses of the tuneable rectangular MPAA for the ON/OFF states as obtained from
the time-domain solver of the CST-MWS are illustrated in Figure 11. The surface current distribution of
the rectangular MPAA design differs from the surface current distribution of the single rectangular MPA
design, so the position of the operating frequency is shifted slightly toward the lower 𝑓𝑟. The 3D results of
the gain of the 4×1 tuneable rectangular MPAA at the operating frequencies 𝑓𝑟= 55.94, 56.43, 58.917,
59.647, 59.8295 and 59.9515 GHz are illustrated in Figure 12. In order to provide a comparison of
the tuneable single rectangular MPA and the tuneable rectangular MPAA, the gain have been enhanced.
Table 7. Bandwidth results for the tuneable single rectangular MPA
Operating Frequency
(GHz)
Bandwidth
(GHz)
56.329 1.2373
56.724 2.1185
59.043 2.6414
59.743 2.6262
59.901 2.5029
60 2.4051

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Generally, antennas with wide beam widths have a low gain, while antennas with narrow beam
widths lead to higher gain; therefore, an antenna that directs most of its energy into a narrow beam will have
a higher gain. When using the 4×1 tuneable rectangular MPAA, the 3 dB beam width is narrower,
as illustrated in Figure 13. It is observed from Figure 9 and Figure 12; that the gain of the previous designs is
enhanced. Table 8 summarizes the results of the comparison of the tuneable single rectangular MPA and
the tuneable rectangular MPAA.
Figure 11. Return loss vs frequency of the tuneable rectangular MPAA for different values of 𝑉𝐵
(a) (b)
(c) (d)
(e) (f)
Figure 12. Gain of the tuneable rectangular MPAA, (a) 𝑓𝑟 = 55.94 GHz, (b) 𝑓𝑟 = 56.43 GHz,
(c) 𝑓𝑟 = 58.917 GHz, (d) 𝑓𝑟 = 59.647GHz, (e) 𝑓𝑟 = 59.8295 GHz, (f) 𝑓𝑟 = 59.9515 GHz

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(a) (b)
(c) (d)
(e) (f)
Figure 13. Radiation patterns for the 4×1 tuneable rectangular MPAA, (a) 𝑓𝑟 =55.94 GHz,
(b) 𝑓𝑟 = 56.43 GHz, (c) 𝑓𝑟 = 58.917 GHz, (d) 𝑓𝑟 = 59.647GHz, (e) 𝑓𝑟 = 59.8295 GHz, (f) 𝑓𝑟 = 59.9515 GHz
Table 8. Comparison results of the previous designs
Applied (𝑉𝐵)
Tuneable Single Rectangular MPA Tuneable Rectangular MPAA
𝑓𝑟
(GHz)
Gain
(dBi)
Return Loss
(dB)
Bandwidth
(GHz)
𝑓𝑟
(GHz)
Gain
(dBi)
Return
Loss (dB)
Bandwidth
(GHz)
0.5 (OFF) 56.329 6.71 -16.4 1.2373 55.92 11.5 -18.69 1.3487
1 56.724 3.79 -18.6 2.1185 56.43 9.16 -15.8 1.9614
5 59.043 3.81 -16.5 2.6414 58.917 9.06 -15.84 2.705
20 59.743 5.17 -29.6 2.6262 59.647 10.2 -25 2.7766
30 59.901 5.65 -37.5 2.5029 59.829 10.6 -34.8 2.707
40 60 5.95 -27.8 2.4051 59.951 10.9 -41.5 2.6096
7. CONCLUSION
In this paper, reconfigurable hybrid metal-graphene single/array rectangular MPAs have been
simulated and optimized for 5G applications via the CST-MWS package. The approach used in this work
involves using planted graphene strips inside a copper radiating patch to obtain a tuneable antenna with
a reasonable performance. The designed antenna has a good gain and many frequencies in range of 55.75 to
61.26 GHz in the tuneable single rectangular MPA and the same results were obtained in the array
configuration but with some shifting toward the lower 𝑓𝑟 due to the surface current distribution of

5557
the rectangular MPAA design differs from the surface current distribution of the single rectangular MPA
design. This depends on the voltage applied to the graphene strips. From this work, it can be concluded that
increasing the applied voltage on the graphene strips leads to reducing their surface impedances, resulting
a shift in the resonance frequency towards the upper frequency. Finally, the MPA bandwidth is expanded.
As noted from the above-mentioned comparison results involving the tuneable single/array rectangular MPA
designs, the gain has improved significantly.
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 ISSN: 2088-8708
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BIOGRAPHIES OF AUTHORS
Hamzah M. Marhoon received his B.Sc. degree in Electrical Engineering (Rank 2) from
College of Engineering Al-Mustansiriyah University, Baghdad, Iraq in 2016. He obtained his
M.Sc. degree in Communications Engineering in 2020 from Al-Ahliyya Amman University,
Hashemite Kingdom of Jordan. He works as a teaching assistant at Al-Esraa University
College, Baghdad, Iraq. His research interests include Antennas, Tuneable Antennas, IoT,
Energy Harvesting Antennas, and Embedded Systems.
Email: hamzaalazawy33@yahoo.com
ORCID iD: https://orcid.org/0000-0001-5613-6685
Nidal Qasem received his B.Sc. degree in Electronics and Communications Engineering
(Honours) from AL-Ahliyya Amman University, Amman, Jordan, in 2004. He obtained his
M.Sc. degree in Digital Communication Systems for Networks & Mobile Applications
(DSC) from Loughborough University, Loughborough, United Kingdom, in 2006. He then
pursued a PhD degree in wireless and digital communication systems at Loughborough
University. He is currently working as an associate professor in the department of
Electronics and Communications Engineering at Al-Ahliyya Amman University. His
research interests include propagation control in buildings, specifically improving the
received power, FSS measurements and designs, antennas, ultra-wide band, orbital angular
momentum, and wireless system performance analyses. He is a senior member of the IEEE.

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