3 gpp lte physical layer

White Paper

Overview of the 3GPP Long Term
Evolution Physical Layer
Jim Zyren
jzyren@freescale.com
Dr. Wes McCoy, Technical Editor

Document Number: 3GPPEVOLUTIONWP
Rev 0
07/2007

Overview
Long Term Evolution (LTE) is the next step forward in cellular 3G services. Expected in the 2008 time frame, LTE is a
3GPP standard that provides for an uplink speed of up to 50 megabits per second (Mbps) and a downlink speed of up
to 100 Mbps. LTE will bring many technical benefits to cellular networks. Bandwidth will be scalable from 1.25 MHz to 20
MHz. This will suit the needs of different network operators that have different bandwidth allocations, and also allow
operators to provide different services based on spectrum. LTE is also expected to improve spectral efficiency in 3G
networks, allowing carriers to provide more data and voice services over a given bandwidth.

This technical white paper provides an overview of the LTE physical layer (PHY), including technologies that are new to
cellular such as Orthogonal Frequency Division Multiplexing (OFDM) and Multiple Input Multiple Output (MIMO) data
transmission.

Contents
1 Introduction 1 3.1.4 Physical Signals 17

1.1 LTE Design Goals 1 3.1.5 Transport Channels 18
2 LTE Basic Concepts 2 3.1.6 Mapping Downlink Physical
Channels to Transport Channels 19
2.1 Single Carrier Modulation
and Channel Equalization 2 3.1.7 Downlink Channel Coding 19

2.2 OFDM 3 3.2 Uplink 20

2.2.1 Disadvantages of OFDM 5 3.2.1 Modulation Parameters 20

2.3 OFDMA 7 3.2.2 Multiplexing 20

2.3.1 Comparison of OFDMA with Packet- 3.2.3 Uplink Physical Channels 20
Oriented Protocols 7
3.2.4 Uplink Physical Signals 21
2.3.2 OFDMA and the LTE Generic Frame
3.2.5 Uplink Transport Channels 21
Structure 8
3.2.6 Mapping Uplink Physical
2.4 MIMO and MRC 10
Channels to Transport Channels 22
2.5 SC-FDMA 13
3.2.7 Coding 22
3 LTE Physical Layer 14
3.3 MB-SFN 22
3.1 Downlink 15
4 Conclusions 22
3.1.1 Modulation Parameters 15
5 References 23
3.1.2 Downlink Multiplexing 16
6 Acronyms and Abbreviations 24
3.1.3 Physical Channels 16

1 Introduction
The 3GPP Long Term Evolution (LTE) represents a major advance in cellular technology. LTE is designed to meet
carrier needs for high-speed data and media transport as well as high-capacity voice support well into the next decade.
It encompasses high-speed data, multimedia unicast and multimedia broadcast services. Although technical
specifications are not yet finalized, significant details are emerging. This paper focuses on the LTE physical layer
(PHY).

The LTE PHY is a highly efficient means of conveying both data and control information between an enhanced base
station (eNodeB) and mobile user equipment (UE). The LTE PHY employs some advanced technologies that are new
to cellular applications. These include Orthogonal Frequency Division Multiplexing (OFDM) and Multiple Input Multiple
Output (MIMO) data transmission. In addition, the LTE PHY uses Orthogonal Frequency Division Multiple Access
(OFDMA) on the downlink (DL) and Single Carrier – Frequency Division Multiple Access (SC-FDMA) on the uplink (UL).
OFDMA allows data to be directed to or from multiple users on a subcarrier-by-subcarrier basis for a specified number
of symbol periods. Due to the novelty of these technologies in cellular applications, they are described separately
before delving into a description of the LTE PHY.

Although the LTE specs describe both Frequency Division Duplexing (FDD) and Time Division Duplexing (TDD) to
separate UL and DL traffic, market preferences dictate that the majority of deployed systems will be FDD. This paper
therefore describes LTE FDD systems only.

1.1 LTE Design Goals
The LTE PHY is designed to meet the following goals [1]:

1. Support scalable bandwidths of 1.25, 2.5, 5.0, 10.0 and 20.0 MHz

2. Peak data rate that scales with system bandwidth

a. Downlink (2 Ch MIMO) peak rate of 100 Mbps in 20 MHz channel

b. Uplink (single Ch Tx) peak rate of 50 Mbps in 20 MHz channel

3. Supported antenna configurations

a. Downlink: 4x2, 2x2, 1x2, 1x1

b. Uplink: 1x2, 1x1

4. Spectrum efficiency

a. Downlink: 3 to 4 x HSDPA Rel. 6

b. Uplink: 2 to 3 x HSUPA Rel. 6
5. Latency

a. C-plane: <50 – 100 msec to establish U-plane

b. U-plane: <10 msec from UE to server

6. Mobility

A. Optimized for low speeds (<15 km/hr)

B. High performance at speeds up to 120 km/hr

C. Maintain link at speeds up to 350 km/hr

7. Coverage

a. Full performance up to 5 km

b. Slight degradation 5 km – 30 km

c. Operation up to 100 km should not be precluded by standard

Freescale Semiconductor, Inc. Overview of the 3GPP Long Term Evolution Physical Layer 1

2 LTE Basic Concepts
Before jumping into a detailed description of the LTE PHY, it’s worth taking a look at some of the basic technologies
involved. Many methods employed in LTE are relatively new in cellular applications. These include OFDM, OFDMA,
MIMO and Single Carrier Frequency Division Multiple Access (SC-FDMA). Readers familiar with these technologies can
skip this material and proceed directly to Section 3.

LTE employs OFDM for downlink data transmission and SC-FDMA for uplink transmission. OFDM is a well-known
modulation technique, but is rather novel in cellular applications. A brief discussion of the basic properties and
advantages of this method is therefore warranted.

When information is transmitted over a wireless channel, the signal can be distorted due to multipath. Typically (but not
always) there is a line-of-sight path between the transmitter and receiver. In addition, there are many other paths
created by signal reflection off buildings, vehicles and other obstructions as shown in Figure 2.0-1. Signals traveling
along these paths all reach the receiver, but are shifted in time by an amount corresponding to the differences in the
distance traveled along each path.

2.1 Single Carrier Modulation and Figure 2.0-1 Multipath is Caused by Reflections
Channel Equalization Off Objects Such as Buildings and Vehicles
To date, cellular systems have used single carrier
modulation schemes almost exclusively. Although LTE
uses OFDM rather than single carrier modulation, it’s
instructive to briefly discuss how single carrier systems
deal with multipath-induced channel distortion. This will
form a point of reference from which OFDM systems can
be compared and contrasted.

The term delay spread describes the amount of time
delay at the receiver from a signal traveling from the
transmitter along different paths. In cellular applications,
delay spreads can be several microseconds. The delay induced by multipath can cause a symbol received along a
delayed path to “bleed” into a subsequent symbol arriving at the receiver via a more direct path. This effect is depicted
in Figure 2.1-1 and is referred to as inter-symbol interference (ISI). In a conventional single carrier system symbol times
decrease as data rates increase. At very high data rates (with correspondingly shorter symbol periods), it is quite
possible for ISI to exceed an entire symbol period and spill into a second or third subsequent symbol.
Figure 2.1-1 Multipath-Induced Time Delays Result in ISI

Delayed signal rec’d
via longer path
ISI ISI ISI

Signal received
by direct path

It’s also helpful to consider the effects of multipath distortion in the frequency domain. Each different path length and
reflection will result in a specific phase shift. As all of the signals are combined at the receiver, some frequencies within
the signal passband undergo constructive interference (linear combination of signals in-phase), while others encounter
destructive interference (linear combination of signals out-of-phase). The composite received signal is distorted by
frequency selective fading (see Figure 2.1-2).

2 Overview of the 3GPP Long Term Evolution Physical Layer Freescale Semiconductor

Figure 2.1-2 Longer Delay Spreads Result in Frequency Selective Fading

Signal Bandwidth Signal Bandwidth deep fades

Multipath
Distortion

frequency frequency

Transmitted Single Carrier Signal Received Signal Distorted by
Frequency Selective Fading

Single carrier systems compensate for channel distortion via time domain equalization. This is a substantial topic by
itself, and beyond the scope of this paper. Generally, time domain equalizers compensate for multipath induced
distortion by one of two methods:

1. Channel inversion: A known sequence is transmitted over the channel prior to sending information. Because
the original signal is known at the receiver, a channel equalizer is able to determine the channel response and
multiply the subsequent data-bearing signal by the inverse of the channel response to reverse the effects of
multipath.

2. CDMA systems can employ rake equalizers to resolve the individual paths and then combine digital copies of
the received signal shifted in time to enhance the receiver signal-to-noise ratio (SNR).

In either case, channel equalizer implementation becomes increasingly complex as data rates increase. Symbol times
become shorter and receiver sample clocks must become correspondingly faster. ISI becomes much more severe—
possibly spanning several symbol periods.
Figure 2.1-3 Transversal Filter Channel Equalizer

τ τ τ τ τ

Σ

Adaptive
Algorithm

The finite impulse response transversal filter (see Figure 2.1-3) is a common equalizer topology. As the period of the
receiver sample clock (τ) decreases, more samples are required to compensate for a given amount of delay spread.
The number of delay taps increases along with the speed and complexity of the adaptive algorithm. For LTE data rates
(up to 100 Mbps) and delay spreads (approaching 17 μsec), this approach to channel equalization becomes
impractical. As we will discuss below, OFDM eliminates ISI in the time domain, which dramatically simplifies the task of
channel compensation.

2.2 OFDM
Unlike single carrier systems described above, OFDM communication systems do not rely on increased symbol rates in
order to achieve higher data rates. This makes the task of managing ISI much simpler. OFDM systems break the
available bandwidth into many narrower sub-carriers and transmit the data in parallel streams. Each subcarrier is
modulated using varying levels of QAM modulation, e.g. QPSK, QAM, 64QAM or possibly higher orders depending on
signal quality. Each OFDM symbol is therefore a linear combination of the instantaneous signals on each of the sub-


carriers in the channel. Because data is transmitted in parallel rather than serially, OFDM symbols are generally MUCH
longer than symbols on single carrier systems of equivalent data rate.

There are two truly remarkable aspects of OFDM. First, each OFDM symbol is preceded by a cyclic prefix (CP), which
is used to effectively eliminate ISI. Second, the sub-carriers are very tightly spaced to make efficient use of available
bandwidth, yet there is virtually no interference among adjacent sub-carriers (Inter Carrier Interference, or ICI). These
two unique features are actually closely related. In order to understand how OFDM deals with multipath distortion, it’s
useful to consider the signal in both the time and frequency domains.

To understand how OFDM deals with ISI induced by multipath, consider the time domain representation of an OFDM
symbol shown in Figure 2.2-1. The OFDM symbol consists of two major components: the CP and an FFT period
(TFFT). The duration of the CP is determined by the highest anticipated degree of delay spread for the targeted
application. When transmitted signals arrive at the receiver by two paths of differing length, they are staggered in time
as shown in Fig. 2.2-2.
Figure 2.2-2 OFDM Eliminates ISI via Longer Symbol Periods and a Cyclic Prefix

Signal delay < CP

Signals with varying
delays combine
at receiver front end

CP = TFFT =
4.6875 μsec 66.667 μsec
Baseband processor
strips off CP, resulting
in RECT functions in
time domain

Within the CP, it is possible to have distortion from the preceding symbol. However, with a CP of sufficient duration,
preceding symbols do not spill over into the FFT period; there is only interference caused by time-staggered “copies” of
the current symbol. Once the channel impulse response is determined (by periodic transmission of known reference
signals), distortion can be corrected by applying an amplitude and phase shift on a subcarrier-by-subcarrier basis.

Note that all of the information of relevance to the receiver is contained within the FFT period. Once the signal is
received and digitized, the receiver simply throws away the CP. The result is a rectangular pulse that, within each
subcarrier, is of constant amplitude over the FFT period.
The rectangular pulses resulting from decimation of the CP are central to the ability to space subcarriers very closely in
frequency without creating ICI. Readers may recall that a uniform rectangular pulse (RECT function) in the time domain
results in a SINC function (sin(x) / x) in the frequency domain as shown in Fig. 2.2-3. The LTE FFT Period is 67.77
μsec. Note that this is simply the inversion of the carrier spacing (1 / Δf). This results in a SINC pattern in the frequency
domain with uniformly spaced zero-crossings at 15 kHz intervals—precisely at the center of the adjacent subcarrier. It is
therefore possible to sample at the center frequency of each subcarrier while encountering no interference from
neighboring subcarriers (zero-ICI).


Figure 2.2-3 FFT of OFDM Symbol Reveals Distinct Subcarriers
amplitude

amplitude
OFDM symbol is
linear summation
of subcarriers

time time
TFFT TFFT

freq

Baseband FFT resolves
individual subcarriers

amplitude

fc freq

2.2.1 Disadvantages of OFDM
As we have seen, OFDM has some remarkable attributes. However, like all modulation schemes, it suffers from some
drawbacks. OFDM has two principle weaknesses relative to single carrier systems: susceptibility to carrier frequency
errors (due either to local oscillator offset or Doppler shifts) and a large signal peak-to-average power ratio (PAPR).

As discussed above, OFDM systems can achieve zero-ICI if each subcarrier is sampled precisely at its center
frequency. The time-sampled OFDM signal is converted into the frequency domain by means of a fast Fourier transform
(FFT)—which is a highly efficient means of implementing a discrete Fourier transform (DFT). The DFT renders a
discrete finite sequence of complex coefficients which are given by:
N −1
X k = ∑ x n e − j 2πnk / N , k = 0, 1,…N-1
n =0

The resulting Fourier spectrum has discrete frequencies at:
k/NTs, k = 0, 1,…N-1
where Ts is the sample interval in the time domain and N is the number of samples. Thus, the frequencies in the Fourier
representation are completely defined by the sample frequency (1 / Ts) and the number of samples taken within the FTT
period.

Let’s consider a specific LTE example. LTE defines transmission bandwidths from 1.25 MHz up to 20 MHz. In the case
of 1.25 MHz transmission bandwidth, the FFT size is 128. In other words, 128 samples are taken within the FFT period
of 66.67 μsec. Therefore, Ts = 0.52086 μsec, and the received signal is represented by frequencies at 15 kHz, 30 kHz,
45 kHz… These frequencies are the exact center frequencies of the signal subcarriers—unless frequency errors are
encountered in the downconversion process.

The FFT is done at baseband frequency, after the received signal has been downconverted from the RF carrier
frequency. Downconversion is typically performed by means of direct conversion. The received signal is mixed with a
signal produced by the receiver’s local oscillator (LO). Ideally, the carrier signal and the receiver LO are at the identical
frequency. Unfortunately, this is not always the case.

The transmitter and receiver local oscillators will invariably drift, so active means must be taken to keep them
synchronized. Each base station periodically sends synchronization signals which are used by the UE for this purpose,
among other things (synchronization signals are also used for initial acquisition and handover). Even so, other sources


such as Doppler shifts and oscillator phase noise can still result in frequency errors. Uncorrected frequency errors will
result in ICI as shown in Figure 2.2.1-1. For these reasons, the signal frequency must be tracked continuously. Any
offsets must be corrected in the baseband processor to avoid excessive ICI that might result in dropped packets.
Figure 2.2-1.1 Uncorrected Frequency Errors Cause ICI

2
FFT points

1.5 Demodulated
zero ICI Signal without
Frequency Offset
Normalized Voltage

1 (Zero ICI)

0.5

0

-0.5
15 30 45 60 75 90 105
Frequency (kHz)

2
ICI induced by
freq. error freq. error
1.5
Demodulated
Signal with
Normailized Voltage

1 Frequency Offset
Causing ICI

0.5

0

-0.5
15 30 45 60 75 90 105
Frequency (kHz)

The other major drawback to OFDM is a high PAPR. The instantaneous transmitted RF power can vary dramatically
within a single OFDM symbol. As stated above, the OFDM symbol is a combination of all of the subcarriers. Subcarrier


voltages can add in-phase at some points within the symbol, resulting in very high instantaneous peak power—much
higher than the average power.

A high PAPR drives dynamic range requirements for A/D and D/A converters. Even more importantly, it also reduces
efficiency of the transmitter RF power amplifier (RFPA). Single carrier systems sometimes use constant envelope
modulation methods, such as Gaussian Minimum Shift Keying (GMSK) or Phase Shift Keying (PSK). The information in
the signal of a single carrier system is conveyed by varying the instantaneous frequency or phase while the signal
amplitude remains constant. The RFPA does not require a high degree of linearity. In fact, the PA can be driven so hard
that the signal is “clipped” as the signal swings between the minimum and maximum voltages. Harmonic distortion due
to clipping can be eliminated by output filtering. When RFPAs are operated in this manner, they can achieve efficiencies
on the order of 70 percent.

In contrast, OFDM is not a constant envelope modulation scheme. Within each symbol, the amplitude and phase of
each sub-carrier is constant. Over the duration of an OFDM symbol, there can be several large peaks. The RFPA must
be capable of handling peak voltage swings without clipping, thus requiring a larger amplifier to handle a given average
power. Efficiency is therefore lower. RFPA efficiencies for OFDM signals can be less than 20 percent. Although there
are measures that can be taken to reduce voltage peaks, PAPR for OFDM results in RFPA efficiencies that are
generally lower than for single-carrier constant envelope systems.

2.3 OFDMA
OFDMA is employed as the multiplexing scheme in the LTE downlink. Perhaps the best way to describe OFDMA is by
contrasting it with a packet-oriented networking scheme such as 802.11a. In 802.11a, Carrier-Sense Multiple Access
(CSMA) is the multiplexing method. Downlink and uplink traffic from the fixed access point (AP) to mobile user stations
(STAs) is by means of PHY layer packets. As explained below, OFDMA makes much more efficient use of network
resources.

2.3.1 Comparison of OFDMA with Packet-Oriented Protocols
Like 3GPP LTE, IEEE 802.11a uses OFDM as the underlying modulation method. However, 802.11a uses CSMA as
the multiplexing method. CSMA is essentially a listen-before-talk scheme. For example, when the AP has queued traffic
for a STA, it monitors the channel for activity. When the channel becomes idle, it begins to decrement an internal timer
that is randomized within a specified window. The timer will continue to be decremented as long as the network remains
idle. When the timer reaches zero, the AP will transmit a PHY layer packet of up to 2000 bytes addressed to a particular
STA (or all STAs within the cell in the case of broadcast mode). The randomized back-off period is designed to
minimize collisions, but it cannot eliminate them entirely.
Figure 2.3.1-1 Conventional Packet Oriented Networks Like IEEE 802.11a Precede Each Data Transmission
with a PHY Layer Preamble and Header

1 OFDM Symbol (4 usec)
RATE Reserved LENGTH Parity Tail
4 bits 1 bit 12 bits 1 bit 6 bits

PHY
PHY preamble header
data

Each 802.11a PHY packet utilizes all of the PHY layer bandwidth for the duration of the packet. Consider the 802.11a
PHY packet format shown in Figure 2.3.1-1. Each 802.11a packet has a data payload of varying length from 64 to 2048
bytes. If the packet transmission is successful, the receiving station transmits an ACK. Unacknowledged packets are
assumed to be dropped. Note that each packet is preceded by a PHY preamble which is 20 μsec in duration. The
purposes of the PHY preamble are:

• Signal detection

• Antenna diversity selection


• Setting AGC

• Frequency offset estimation

• Timing synchronization

• Channel estimation

The address of the intended recipient is not in the PHY preamble. It is actually in the packet data and is interpreted at
the MAC layer. From a networking perspective, the packet-oriented approach of 802.11a has the advantage of
simplicity. Each packet is addressed to a single recipient (broadcast mode not withstanding). However, the randomized
backoff period of the CSMA multiplexing scheme is idle time and therefore represents an inefficiency. The PHY
preamble is also network overhead and further reduces efficiency, particularly for shorter packets.

The typical real-world efficiency of an 802.11a system is approximately 50 percent. In other words, for a network with a
nominal data rate of 54 Mbps, the typical throughput is about 25 – 30 Mbps. Some of the inefficiencies can be mitigated
by abandoning the CSMA multiplexing scheme and adopting a scheduled approach to packet transmission. Indeed,
subsequent versions of the 802.11 protocol include this feature. Inefficiencies due to dedicated ACK packets can also
be reduced by acknowledging packets in groups rather than individually.

In spite of potential improvements, it remains difficult to drive packet-oriented network efficiency much beyond 65 to 70
percent. Further, because each packet completely consumes all network resources during transmission and
acknowledgement, the AP can provide addressed (non-broadcast) traffic to user terminals only on a sequential basis.
When many users are active within the cell, latency can become a significant problem. Clearly, the objective of cellular
carriers is to create as much network demand as possible for a wide variety of traffic that includes voice, multimedia,
and data. Efficiency and low latency are therefore paramount. As we will see in the following section, OFDMA is
superior to packet-oriented schemes in both of these critical dimensions.

2.3.2 OFDMA and the LTE Generic Frame Structure
OFDMA is an excellent choice of multiplexing scheme for the 3GPP LTE downlink. Although it involves added
complexity in terms of resource scheduling, it is vastly superior to packet-oriented approaches in terms of efficiency and
latency. In OFDMA, users are allocated a specific number of subcarriers for a predetermined amount of time. These are
referred to as physical resource blocks (PRBs) in the LTE specifications. PRBs thus have both a time and frequency
dimension. Allocation of PRBs is handled by a scheduling function at the 3GPP base station (eNodeB).
Figure 2.3.2-1 LTE Generic Frame Structure

1 Frame (10 msec)

1 Sub-Frame (1.0 msec) 1 Slot (0.5 msec)

0 1 2 3 10 11 19

0 1 2 3 4 5 6 0 1 2 3 4 5 6

7 OFDM Symbols
(short cyclic prefix)
cyclic prefixes

In order to adequately explain OFDMA within the context of the LTE, we must study the PHY layer generic frame
structure. The generic frame structure is used with FDD. Alternative frame structures are defined for use with TDD.
However, TDD is beyond the scope of this paper. Alternative frame structures are therefore not considered.

As shown in figure 2.3.2-1, LTE frames are 10 msec in duration. They are divided into 10 subframes, each subframe
being 1.0 msec long. Each subframe is further divided into two slots, each of 0.5 msec duration. Slots consist of either 6
or 7 ODFM symbols, depending on whether the normal or extended cyclic prefix is employed.


Table 2.3.2-1 Available Downlink Bandwidth is Divided into Physical Resource Blocks

Bandwidth (MHz) 1.25 2.5 5.0 10.0 15.0 20.0

Subcarrier bandwidth (kHz) 15

Physical resource block (PRB) 180
bandwidth (kHz)

Number of available PRBs 6 12 25 50 75 100

The total number of available subcarriers depends on the overall transmission bandwidth of the system. The LTE
specifications define parameters for system bandwidths from 1.25 MHz to 20 MHz as shown in Table 2.3.2-1. A PRB is
defined as consisting of 12 consecutive subcarriers for one slot (0.5 msec) in duration. A PRB is the smallest element of
resource allocation assigned by the base station scheduler.
Figure 2.3.2-2 Downlink Resource Grid

Tslot
downlink slot

Resource Block:

7 symbols X 12 subcarriers (short CP), or;
NBW subcarriers

12 subcarriers

6 symbols X 12 subcarriers (long CP)

Resource Element


The transmitted downlink signal consists of NBW subcarriers for a duration of Nsymb OFDM symbols. It can be
represented by a resource grid as depicted in Figure 2.3.2-2. Each box within the grid represents a single subcarrier for
one symbol period and is referred to as a resource element. Note that in MIMO applications, there is a resource grid for
each transmitting antenna.

In contrast to packet-oriented networks, LTE does not employ a PHY preamble to facilitate carrier offset estimate,
channel estimation, timing synchronization etc. Instead, special reference signals are embedded in the PRBs as shown
in Figure 2.3.2-3. Reference signals are transmitted during the first and fifth OFDM symbols of each slot when the short
CP is used and during the first and fourth OFDM symbols when the long CP is used.
Figure 2.3.2-3 LTE Reference Signals are Interspersed Among Resource Elements

Subframe

Slot Slot

R R
12 Subcarriers

R R

R R

R R

Note that reference symbols are transmitted every sixth subcarrier. Further, reference symbols are staggered in both
time and frequency. The channel response on subcarriers bearing the reference symbols can be computed directly.
Interpolation is used to estimate the channel response on the remaining subcarriers.

2.4 MIMO and MRC
The LTE PHY can optionally exploit multiple transceivers at both the basestation and UE in order to enhance link
robustness and increase data rates for the LTE downlink. In particular, maximal ratio combining (MRC) is used to
enhance link reliability in challenging propagating conditions when signal strength is low and multipath conditions are
challenging. MIMO is a related technique that is used to increase system data rates.
Figure 2.4-1a Figure 2.4-1b
MRC/MIMO Operation Requires Multiple Transceivers

XCVR-A
Baseband XCVR Baseband
XCVR-B

Conventional Single Channel MRC/MIMO Receiver
Receiver w/Antenna Diversity Configuration (2-ch)


Figure 2.4-1a shows a conventional single channel receiver with antenna diversity. This receiver structure uses multiple
antennas, but it is not capable of supporting MRC/MIMO. The basic receiver topology for both MRC and MIMO is
shown in Figure 2.4-1b. MRC and MIMO are sometimes referred to as “multiple antenna” technologies, but this is a bit
of a misnomer. Note that the salient difference between the receivers shown in Figures 2.4-1a and 2.4-1b is not multiple
antennas, but rather multiple transceivers.

With MRC, a signal is received via two (or more) separate antenna/transceiver pairs. Note that the antennas are
physically separated, and therefore have distinct channel impulse responses. Channel compensation is applied to each
received signal within the baseband processor before being linearly combined to create a single composite received
signal.

When combined in this manner, the received signals add coherently within the baseband processor. However, the
thermal noise from each transceiver is uncorrelated. Thus, linear combination of the channel compensated signals at
the baseband processor results in an increase in SNR of 3 dB on average for a two-channel MRC receiver in a noise-
limited environment.
Fig. 2.4-2 MRC Enhances Reliability in the Presence of AWGN and Frequency Selective Fading

deep fades deep fades

freq freq
Signal from Transceiver A MRC Signal from Transceiver B
Combining

freq

SNR for All Subcarriers Enhanced
in Composite MRC Signal

Aside from the improvement in SNR due to combining, MRC receivers are robust in the presence of frequency selective
fading. Recall that physical separation of the receiver antennas results in distinct channel impulse responses for each
receiver channel. In the presence of frequency selective fading, it is statistically unlikely that a given subcarrier will
undergo deep fading on both receiver channels. The possibility of deep frequency selective fades in the composite
signal is therefore significantly reduced.

MRC enhances link reliability, but it does not increase the nominal system data rate. In MRC mode, data is transmitted
by a single antenna and is processed at the receiver via two or more receivers. MRC is therefore a form of receiver
diversity rather than more conventional antenna diversity. MIMO, on the other hand, does increase system data rates.
This is achieved by using multiple antennas on both the transmitting and receiving ends.


Figure 2.4-3 Reference Signals Transmitted Sequentially to Compute Channel Responses for
MIMO Operation

OFDM Symbols
(time)

R0 R0 R1 R1

R0 Reference Signal
from Antenna 0
Subcarriers
(frequency)

R0 R0 R1 R1
Reference Signal
R1 from Antenna 1

R0 R0 R1 R1 Denotes Unused
Resource Element

R1
R0 R0 R1

Antenna 0 Antenna 1
In order to successfully receive a MIMO transmission, the receiver must determine the channel impulse response from
each transmitting antenna. In LTE, channel impulse responses are determined by sequentially transmitting known
reference signals from each transmitting antenna as shown in Figure 2.4-3.
Figure 2.4-4 MIMO Operation Requires A Priori Knowledge of all Channel Responses
ChAC

Ch
AD

XCVR-A XCVR-C
SC = REFA x ChAC
Baseband Baseband
XCVR-B SD = REFA x ChAD XCVR-D

Reference Signal Transmitted from Antenna A

Ch BC

ChBD
XCVR-A XCVR-C
Baseband Baseband
SC = REFB x ChBC
XCVR-B XCVR-D
SD = REFB x ChBD

Reference Signal Transmitted from Antenna B

XCVR-A XCVR-C
Baseband SC = [DATAA x ChAC] + [DATAB x ChBC] Baseband
XCVR-B XCVR-D
SD = [DATAA x ChAD] + [DATAB x ChBD]

Data Transmitted Simultaneously from BOTH Antennas

Referring to the 2 x 2 MIMO system in Figure 2.4-4, there are a total of four channel impulse responses (C1, C2, C3 and
C4). Note that while one transmitter antenna is sending the reference signal, the other antenna is idle. Once the channel


impulse responses are known, data can be transmitted from both antennas simultaneously. The linear combination of
the two data streams at the two receiver antennas results in a set of two equations and two unknowns, which is
resolvable into the two original data streams.

2.5 SC-FDMA
LTE uplink requirements differ from downlink requirements in several ways. Not surprisingly, power consumption is a
key consideration for UE terminals. The high PAPR and related loss of efficiency associated with OFDM signaling are
major concerns. As a result, an alternative to OFDM was sought for use in the LTE uplink.

Single Carrier – Frequency Domain Multiple Access (SC-FDMA) is well suited to the LTE uplink requirements. The
basic transmitter and receiver architecture is very similar (nearly identical) to OFDMA, and it offers the same degree of
multipath protection. Importantly, because the underlying waveform is essentially single-carrier, the PAPR is lower.
Fig. 2.5-1 SC-FDMA and OFDMA Signal Chains Have a High Degree of Functional Commonality

Cyclic
Single
Symbol N-Point Prefix
Bit Carrier S/P M-Point Subcarrier
IDFT & RFE
Stream Constellation Convert DFT Mapping
Block Pulse
Mapping
Shaping
Channel

Freq Cyclic
Bit Const. SC P/S Symbol M-Point N-Point
Detector Convert Domain DFT Prefix RFE
Stream De-map IDFT
Block Equalizer Removal

Functions Common to OFDMA and SC-FDMA

SC-FDMA Only

The block diagram of Figure 2.5-1 shows a basic SC-FDMA transmitter / receiver arrangement. Note that many of the
functional blocks are common to both SC-FDMA and OFDMA, thus there is a significant degree of functional
commonality between the uplink and downlink signal chains. The functional blocks in the transmit chain are:
1. Constellation mapper: Converts incoming bit stream to single carrier symbols (BPSK, QPSK, or 16QAM
depending on channel conditions)
2. Serial/parallel converter: Formats time domain SC symbols into blocks for input to FFT engine

3. M-point DFT: Converts time domain SC symbol block into M discrete tones

4. Subcarrier mapping: Maps DFT output tones to specified subcarriers for transmission. SC-FDMA systems
either use contiguous tones (localized) or uniformly spaced tones (distributed) as shown in Figure 2.5-2. The
current working assumption in LTE is that localized subcarrier mapping will be used. The trades between
localized and distributed subcarrier mapping are discussed further below.
5. N-point IDFT: Converts mapped subcarriers back into time domain for transmission

6. Cyclic prefix and pulse shaping: Cyclic prefix is pre-pended to the composite SC-FDMA symbol to provide
multipath immunity in the same manner as described for OFDM. As in the case of OFDM, pulse shaping is
employed to prevent spectral regrowth.
7. RFE: Converts digital signal to analog and upconvert to RF for transmission

In the receive side chain, the process is essentially reversed. As in the case of OFDM, SC-FDMA transmissions can be
thought of as linear summations of discrete subcarriers. Multipath distortion is handled in the same manner as in OFDM


systems (removal of CP, conversion to the frequency domain, then apply the channel correction on a subcarrier-by-
subcarrier basis).

Unlike OFDM, the underlying SC-FDMA signal represented by the discrete subcarriers is—not surprisingly—single
carrier. This is distinctly different than OFDM because the SC-FDMA subcarriers are not independently modulated. As a
result, PAPR is lower than for OFDM transmissions. Analysis has shown that the LTE UE RFPA can be operated about
2 dB closer to the 1-dB compression point than would otherwise be possible if OFDM were employed on the uplink [2].
2.5-2 SC-FDMA Subcarriers Can be Mapped in Either Localized or Distributed Mode

freq freq
Localized Subcarriers Distributed Subcarriers

As mentioned above, SC-FDMA subcarriers can be mapped in one of two ways: localized or distributed as shown in
Figure 2.5-2. However, the current working assumption is that LTE will use localized subcarrier mapping. This decision
was motivated by the fact that with localized mapping, it is possible to exploit frequency selective gain via channel-
dependent scheduling (assigning uplink frequencies to UE based on favorable propagation conditions).

3 LTE Physical Layer
The capabilities of the eNodeB and UE are obviously quite different. Not surprisingly, the LTE PHY DL and UL are quite
different. The DL and UL are treated separately within the specification documents. Therefore, the DL and UL are
described separately in the following sections.
3.0.1 Generic Frame Structure

One element shared by the LTE DL and UL is the generic frame structure. As mentioned previously, the LTE
specifications define both FDD and TDD modes of operation. This paper deals exclusively with describing FDD
specifications. The generic frame structure applies to both the DL and UL for FDD operation. It is described in detail
Section 2.3.2 above, and the main points are repeated in this section.
Figure 3.0.1-1 LTE Generic Frame Structure

1 Frame (10 msec)

1 Sub-Frame (1.0 msec) 1 Slot (0.5 msec)

0 1 2 3 10 11 19

0 1 2 3 4 5 6 0 1 2 3 4 5 6

7 OFDM Symbols
(short cyclic prefix)
cyclic prefixes

As described in Section 2.3.2, LTE transmissions are segmented into frames, which are 10 msec in duration. Frames
consist of 20 slot periods of 0.5 msec. Sub-frames contain two slot periods and are 1.0 msec in duration.


3.1 Downlink
The LTE PHY specification is designed to accommodate bandwidths from 1.25 MHz to 20 MHz. OFDM was selected as
the basic modulation scheme because of its robustness in the presence of severe multipath fading. Downlink
multiplexing is accomplished via OFDMA.

The DL supports physical channels, which convey information from higher layers in the LTE stack, and physical signals
which are for the exclusive use of the PHY layer. Physical channels map to transport channels, which are service
access points (SAPs) for the L2/L3 layers. Depending on the assigned task, physical channels and signals use different
modulation and coding parameters.

3.1.1 Modulation Parameters
OFDM is the modulation scheme for the DL. The basic subcarrier spacing is 15 kHz, with a reduced subcarrier spacing
of 7.5 kHz available for some MB-SFN scenarios. Table 3.1.1-1 summarizes OFDM modulation parameters.
Table 3.1.1-1 Downlink OFDM Modulation Parameters

Transmission BW 1.25 MHz 2.5 MHz 5 MHz 10 MHz 15 MHz 20 MHz

Sub-frame duration 0.5 ms

Sub-carrier spacing 15 kHz

Sampling frequency 192 MHz 3.84 MHz 7.68 MHz (2 15.36 MHz 23.04 MHz (6 30.72 MHz
(1/2 x 3.84 x 3.84 MHz) (4 x 3.84 x 3.84 MHz) (8 x 3.84
MHz) MHz) MHz)

FFT size 128 256 512 1024 1536 2048

OFDM sym per slot 7/6
(short/long CP)

CP length Short (4.69/9) x 6, (4.69/18) x 6, (4.69/36) x 6, (4.69/72) x 6, (4.69/108) x 6, (4.69/144) x
(usec/ (5.21/10) x 1 (5.21/20) x 1 (5.21/40) x 1 (5.21/80) x 1 (5.21/120) x 1 6, (5.21/160)
samples) x1

Long (16.67/32) (16.67/64) (16.67/128) (16.67/256) (16.67/384) (16.67/512)

Depending on the channel delay spread, either short or long CP is used. When short CP is used, the first OFDM
symbol in a slot has slightly longer CP than the remaining six symbols, as shown in Table 3.1.1-2. This is done to
preserve slot timing (0.5 msec).
Table 3.1.1-2 Cyclic Prefix Duration

Configuration Cyclic Prefix Length

Ts μsec

Normal CP ∆f = 15 kHz 160 for l = 0 5.21 for l = 0

144 for l = 1, 2…5 4.69 for l = 1, 2…5

Extended CP ∆f = 15 kHz 512 16.67

∆f = 15 kHz 1024 33.33


Note that the CP duration is described in absolute terms (e.g. 16.67 μsec for long CP) and in terms of standard time
units, Ts. Ts is used throughout the LTE specification documents. It is defined as Ts = 1 / (15000 x 2048) seconds, which
corresponds to the 30.72 MHz sample clock for the 2048 point FFT used with the 20 MHz system bandwidth.

3.1.2 Downlink Multiplexing
OFDMA is the basic multiplexing scheme employed in the LTE downlink. OFDMA is a new-to-cellular technology and is
described in detail in Section 2.3.2 above. As described in Section 2.3.2, groups of 12 adjacent subcarriers are grouped
together on a slot-by-slot basis to form physical resource blocks (PRBs). A PRB is the smallest unit of bandwidth
assigned by the base station scheduler.

Referring to Figure 2.3.2-2, a two dimensional (time and frequency) resource grid can be constructed to represent the
transmitted downlink signal. Each block in the grid represents one OFDM symbol on a given subcarrier and is referred
to as a resource element. Note that in MIMO applications, there is one resource grid for each transmitting antenna.

3.1.3 Physical Channels
Three different types of physical channels are defined for the LTE downlink. One common characteristic of physical
channels is that they all convey information from higher layers in the LTE stack. This is in contrast to physical signals,
which convey information that is used exclusively within the PHY layer.
LTE DL physical channels are:

• Physical Downlink Shared Channel (PDSCH)
• Physical Downlink Control Channel (PDCCH)
• Common Control Physical Channel (CCPCH)
Physical channels are mapped to specific transport channels as described in Section 3.1.5 below. Transport channels
are SAPs for higher layers. Each physical channel has defined algorithms for:

• Bit scrambling
• Modulation
• Layer mapping
• CDD precoding
• Resource element assignment
Layer mapping and pre-coding are related to MIMO applications. Basically, a layer corresponds to a spatial multiplexing
channel. MIMO systems are defined in terms of Ntransmitters x Nreceivers. For LTE, defined configurations are 1x 1, 2 x 2,
3 x 2 and 4 x 2. Note that while there are as many as four transmitting antennas, there are only a maximum of two
receivers and thus a maximum of only two spatial multiplexing data streams.

For a 1 x 1 or a 2 x 2 system, there is a simple 1:1 relationship between layers and transmitting antenna ports.
However, for a 3 x 2 and 4 x 2 system, there are still only two spatial multiplexing channels. Therefore, there is
redundancy on one or both data streams. Layer mapping specifies exactly how the extra transmitter antennas are
employed.

Precoding is also used in conjunction with spatial multiplexing. Recall that MIMO exploits multipath to resolve
independent spatial data streams. In other words, MIMO systems require a certain degree of multipath for reliable
operation. In a noise-limited environment with low multipath distortion, MIMO systems can actually become impaired.
Physical Downlink Shared Channel

The PDSCH is utilized basically for data and multimedia transport. It therefore is designed for very high data rates.
Modulation options therefore include QPSK, 16QAM and 64QAM. Spatial multiplexing is also used in the PDSCH. In
fact, spatial multiplexing is exclusive to the PDSCH. It is not used on either the PDCCH or the CCPCH. Layer mapping
for the PDSCH is described in Table 3.1.3-1.


Table 3.1.3-1 PDSCH Layer Mapping

Transmission Number of code Codeword-to-layer mapping
rank words

1 1 x(0)(i) = d(0)(i)

2 2 x(0)(i) = d(0)(i)

x(1)(i) = d(1)(i)

3 2 d(0)(i) is mapped to layer 0

d(1)(i) is mapped to layers 1 and 2

4 2 d(0)(i) is mapped to layers 0 and 1

d(1)(i) is mapped to layers 2 and 3

Physical Downlink Control Channel

The PDCCH conveys UE-specific control information. Robustness rather than maximum data rate is therefore the chief
consideration. QPSK is the only available modulation format. The PDCCH is mapped onto resource elements in up to
the first three OFDM symbols in the first slot of a subframe.
Common Control Physical Channel

The CCPCH carries cell-wide control information. Like the PDCCH, robustness rather than maximum data rate is the
chief consideration. QPSK is therefore the only available modulation format. In addition, the CCPCH is transmitted as
close to the center frequency as possible. CCPCH is transmitted exclusively on the 72 active subcarriers centered on
the DC subcarrier. Control information is mapped to resource elements (k, l) where k refers to the OFDM symbol within
the slot and l refers to the subcarrier. CCPCH symbols are mapped to resource elements in increasing order of index k
first, then l.

3.1.4 Physical Signals
Physical signals use assigned resource elements. However, unlike physical channels, physical signals do not convey
information to/from higher layers. There are two types of physical signals:

• Reference signals used to determine the channel impulse response (CIR)
• Synchronization signals which convey network timing information
Reference Signals

Reference signals are generated as the product of an orthogonal sequence and a pseudo-random numerical (PRN)
sequence. Overall, there are 510 unique reference signals possible. A specified reference signal is assigned to each
cell within a network and acts as a cell-specific identifier.


Figure 2.1.4-1 Resource Element Mapping of Reference Signals
OFDM Symbols
(time)

R0 R0

Subcarriers
(frequency)
1 Antenna

R0 R0

R0 R0

R0 R0
R0 Reference Signal
from Antenna 0
Antenna 0
Reference Signal
R1
from Antenna 1

R0 R0 R1 R1
R2 Reference Signal
2 Antennas

from Antenna 2
R0 R0 R1 R1

Reference Signal
R3
R0 R0 R1 R1 from Antenna 3

R0 R0 R1 R1 Denotes Unused
Resource Element
Antenna 0 Antenna 1

R0 R0 R1 R1 R2 R3 R3
4 Antennas

R0 R0 R1 R1 R2

R0 R0 R1 R1 R2 R3 R3

R0 R0 R1 R1 R2

Antenna 0 Antenna 1 Antenna 2 Antenna 3

As shown in Figure 3.1.4-1, reference signals are transmitted on equally spaced subcarriers within the first and third-
from-last OFDM symbol of each slot. UE must get an accurate CIR from each transmitting antenna. Therefore, when a
reference signal is transmitted from one antenna port, the other antenna ports in the cell are idle.
Reference signals are sent on every sixth subcarrier. CIR estimates for subcarriers that do not bear reference signals
are computed via interpolation. Changing the subcarriers that bear reference signals by pseudo-random frequency
hopping is also under consideration.
Synchronization Signals

Synchronization signals use the same type of pseudo-random orthogonal sequences as reference signals. These are
classified as primary and secondary synchronization signals, depending how they are used by UE during the cell
search procedure. Both primary and secondary synchronization signals are transmitted on the 72 subcarriers centered
around the DC subcarrier during the 0th and 10th slots of a frame (recall there are 20 slots within each frame).

3.1.5 Transport Channels
Transport channels are included in the LTE PHY and act as service access points (SAPs) for higher layers. Downlink
Transport channels are:


Broadcast Channel (BCH)

• Fixed format

• Must be broadcast over entire coverage area of cell
Downlink Shared Channel (DL-SCH)

• Supports Hybrid ARQ (HARQ)

• Supports dynamic link adaption by varying modulation, coding and transmit power

• Suitable for transmission over entire cell coverage area

• Suitable for use with beamforming

• Support for dynamic and semi-static resource allocation

• Support for discontinuous receive (DRX) for power save
Paging Channel (PCH)

• Support for UE DRX

• Requirement for broadcast over entire cell coverage area

• Mapped to dynamically allocated physical resources
Multicast Channel (MCH)

• Requirement for broadcast over entire cell coverage area

• Support for MB-SFN

• Support for semi-static resource allocation

3.1.6 Mapping Downlink Physical Channels to Transport Channels
Transport channels are mapped to physical channels as shown in Figure 3.1.6-1. Supported transport channels are:

1. Broadcast channel (BCH)

2. Paging channel (PCH) Figure 3.1.6-1 Mapping DL Transport Channels to
Physical Channels
3. Downlink shared channel BCH PCH DL-SCH MCH
(DL-SCH) DL Transport
Channels
4. Multicast channel (MCH)

Transport channels provide the following
functions: Under

• Structure for passing data Consideration
to/from higher layers

• Mechanism by which higher DL Physical
Channels
layers can configure the PHY
CCPCH PDSCH PDCCH
• Status indicators (packet error,
CQI etc.) to higher layers

• Support for higher-layer peer-to-peer signaling

3.1.7 Downlink Channel Coding
Different coding algorithms are employed for the DL physical channels. For the common control channel (CCPCH),
modulation is restricted to QPSK. The PDSCH uses up to 64 QAM modulation. For control channels, coverage is the
paramount requirement. Convolutional coding has been selected for use with the CCPCH, though a final determination
regarding code rate has not yet been made.


On the PDSCH, higher-complexity modulation is employed to achieve the highest possible downlink data rates. The
PDSCH uses QPSK, 16QAM, or 64QAM depending on channel conditions. As a result, coding gain is emphasized over
latency. Rate 1/3 turbo coding has been selected for the PDSCH.

3.2 Uplink
The LTE PHY uses Single Carrier - Frequency Division Multiple Access (SC-FDMA) as the basic transmission scheme
for the uplink. The basic operating principles of SC-FDMA are described in Section 2.5 above. SC-FDMA is a
misleading term, since SC-FDMA is essentially a multi-carrier scheme that re-uses many of the functional blocks
included in the UE OFDM receiver signal chain (see Fig. 2.5-1). The principle advantage of SC-FDMA over
conventional OFDM is a lower PAPR (by approximately 2 dB) than would otherwise be possible using OFDM.

3.2.1 Modulation Parameters
In FDD applications, the uplink uses the same generic frame structure (see Section 3.0.1) as the downlink. It also uses
the same subcarrier spacing of 15 kHz and PRB width (12 subcarriers). Downlink modulation parameters (including
normal and extended CP length) are identical to the uplink parameters shown in Tables 3.1.1-1 and 3.1.1-2. Subcarrier
modulation is, however, much different.

In the uplink, data is mapped onto a signal constellation that can be QPSK, 16QAM, or 64QAM depending on channel
quality. However, rather than using the QPSK/QAM symbols to directly modulate subcarriers (as is the case in OFDM),
uplink symbols are sequentially fed into a serial/parallel converter and then into an FFT block as shown in Figure 2.5-1.
The result at the output of the FFT block is a discrete frequency domain representation of the QPSK/QAM symbol
sequence.

The discrete Fourier terms at the output of the FFT block are then mapped to subcarriers before being converted back
into the time domain (IFFT). The final step prior to transmission is appending a CP. It is interesting to note that while the
SC-FDMA signal has a lower PAPR in the time domain, individual subcarrier amplitudes can actually vary more in the
frequency domain than a comparable OFDM signal.

3.2.2 Multiplexing
Uplink PRBs are assigned to UE by the base station scheduler via the downlink CCPCH. Uplink PRBs consist of a
group of 12 contiguous subcarriers for a duration of one slot time.

3.2.3 Uplink Physical Channels
Uplink physical channels are used to transmit information originating in layers above the PHY. Defined UL physical
channels are:
Physical Uplink Shared Channel (PUSCH)

Resources for the PUSCH are allocated on a sub-frame basis by the UL scheduler. Subcarriers are allocated in
multiples of 12 (PRBs) and may be hopped from sub-frame to sub-frame. The PUSCH may employ QPSK, 16QAM or
64QAM modulation.
Physical Uplink Control Channel (PUCCH) Figure 3.2.3-1 PUCCH is Hopped at Slot Boundary

As the name implies, the PUCCH carries
resource i resource j
uplink control information. It is never
transmitted simultaneously with PUSCH data.
PUCCH conveys control information including
slot boundary

channel quality indication (CQI), ACK/NACK,
frequency

HARQ and uplink scheduling requests. The
PUCCH transmission is frequency hopped at
the slot boundary as shown in Figure 3.2.3-1
for added reliability.

resource j resource i

subframe


3.2.4 Uplink Physical Signals
Uplink physical signals are used within the PHY and do not convey information from higher layers. Two types of UL
physical signals are defined: the reference signal and the random access preamble.
Uplink Reference Signal

There are actually two variants of the UL reference signal. The demodulation signal facilitates coherent demodulation. It
is transmitted in the fourth SC-FDMA symbol of the slot and is the same size as the assigned resource. There is also a
sounding reference signal used to facilitate frequency dependent scheduling. Both variants of the UL reference signal
are based on Zadhoff-Chu sequences.
Random Access Preamble

The random access procedure involves the PHY and higher layers. At the PHY layer, the cell search procedure is
initiated by transmission of the random access preamble by the UE. If successful, a random access response is
received from the base station. The random access preamble format is shown in Figure 3.2.4-1. It consists of a cyclic
prefix, a preamble and a guard time during which there is no signal transmitted.
Figure 3.2.4-1 Random Access Preamble Format

TRA

CP Preamble GT

TCP TPRE TGT

For the generic frame structure, the timing parameters are:

TRA: 30720 TS

TGT: 3152 TS

TPRE: 24576 TS

where TS = period of a 30.72 MHz clock

Random access preambles are derived from Zadoff-Chu sequences. They are transmitted on blocks of 72 contiguous
subcarriers allocated for random access by the base station. In FDD applications, there are 64 possible preamble
sequences per cell.

The exact frequency used for transmission of the random access preamble is selected from available random access
channels by higher layers in the UE. Other information provided to the PHY by higher layers includes:

• Available random access channels

• Preamble format (which preamble sequences)

• Initial transmission power

• Power ramp step size

• Maximum number of retries

3.2.5 Uplink Transport Channels
As in the DL, uplink transport channels act as service access points for higher layers. Characteristics of UL transport
channels are described below.
Uplink – Shared Channel (UL-SCH)

• Support possible use of beam forming

• Support dynamic link adaption (varying modulation, coding and/or Tx power)

• Support for HARQ


• Support for dynamic and semi-static resource allocation
Random Access Channel (RACH)

• Supports transmission of limited control information

• Possible risk of collision

3.2.6 Mapping Uplink Physical Channels to Transport Figure 3.2.6-1 Mapping of UL Transport Channels
Channels to UL Physical Channels
Transport channels are mapped to physical channels as BCH UL-SCH
shown in Figure 3.2.6-1. UL Transport
Channels
3.2.7 Coding
The UL-SCH uses the same rate 1/3 turbo encoding scheme
UL Physical
(two 8-state constituent encoders and one internal Channels
interleaver) as the DL-SCH. PRACH PUCCH PUSCH

3.3 MB-SFN
Multimedia Broadcast Multicast Services (MBMS) are performed either in a single cell or multi-cell mode. In single cell
transmissions, MBMS traffic is mapped to the DL-SCH. In multi-cell mode, transmissions from cells are carefully
synchronized to form a Multicast/Broadcast – Single Frequency Network (MB-SFN).

MB-SFN is an elegant application of OFDM for cellular broadcast. The principle of operation is quite simple. Identical
transmissions are broadcast from closely coordinated cells simultaneously on a common frequency. Signals from
adjacent cells arrive at the receiver and are dealt with in the same manner as multipath delayed signals. In this manner,
UE can combine the energy from multiple transmitters with no additional receiver complexity.

If the UE is at a cell boundary, the relative delay between the two signals is quite small. However, if the UE is close to
one base station and relatively distant from a second base station, the amount of delay between the two signals can be
quite large. For this reason, MB-SFN transmissions are supported using a 7.5 kHz subcarrier spacing and a longer CP.
MB-SFN networks also use a common reference signal from all transmitters within the network to facilitate channel
estimation.

As a consequence of the MB-SFN transmission scheme, UE can roam between cells with no handoff procedure
required. Signals from various cells will vary in strength and in relative delay, but in aggregate the received signal is still
dealt with in the same manner as a conventional single channel OFDM transmission.

4 Conclusions
Although incomplete, the LTE specifications do contain a great deal of useful information. It is entirely possible to
construct a reasonably accurate picture of the LTE physical layer at this time. This discussion has hopefully provided
the reader with a reasonably complete description of the LTE PHY. In some cases, material has been omitted for the
sake of brevity. In other instances, the LTE specifications do not contain much detail at this time. As mentioned above,
work on the 3GPP LTE specification is on going at this time and will not be complete before late this year or possibly
early 2008.


5 References

1. 3GPP TR 25.913 - v7.3.0, Requirements for EUTRA and EUTRAN,
http://www.3gpp.org/ftp/Specs/archive/25%5Fseries/25.913/
2. Van Nee and Prasad, OFDM for Wireless Multimedia Communications, Artech House Publishers,
ISBN 0-890006-530-6, 2000
3. T Doc #R1-060023, Cubic Metric in 3GPP-LTE, Motorola, Helsinki, January 2006
4. 3GPP TS 36.300 – v8.0.0, E-UTRA and E-UTRAN Overall Description,
5. 3GPP TS 36.201 – v1.0.0, LTE Physical Layer – General Description,
6. 3GPP TS 36.211 – v1.0.0, Physical Channels and Modulation,
7. 3GPP TS 36.212 – Multiplexing and Channel Coding,
8. 3GPP TS 36.213 – v1.0.0, Physical Layer Procedures,
9. 3GPP TS 36.214 – v0.1.0, Physical Layer – Measurements,
10. 3GPP TS 36.300 v8.0.0, E-UTRA and E-UTRAN Overall Description; Stage 2,


6 Acronyms and Abbreviations
16QAM 16 point quadrature amplitude modulation MBMS Multimedia broadcast multicast service
3GPP Third Generation Partnership Project MB-SFN Multicast/broadcast – single frequency
64QAM 64 point quadrature amplitude modulation network
ACK Acknowledgement MCH Multicast channel
AGC Automatic gain control MIMO Multiple Input Multiple Output
AP Access point MRC Maximal ratio combining
ARQ Automatic repeat request NACK Not acknowledgement
BCH Broadcast channel OFDM Orthogonal Frequency Division
BPSK Binary phase shift keying Multiplexing

BW Bandwidth PAPR Peak-to-average power ratio

CCPCH Common control physical channel PCH Paging channel

CDD Cyclic delay diversity PDCCH Physical downlink control channel

CDMA Code Division Multiple Access PDSCH Physical downlink shared channel

CIR Channel impulse response PHY Physical layer

CP Cyclic prefix PRACH Physical random access channel

CQI Channel quality indication PRB Physical resource block

CSMA Carrier sense multiple access PRN Pseudo random numerical sequence

DC Direct current PSK Phase shift keying

DFT Discrete Fourier transform PUCCH Physical uplink control channel

DL Downlink PUSCH Physical uplink shared channel

DL-SCH Downlink-shared channel QAM Quadrature amplitude modulation

DRX Discontinuous receive QPSK Quadrature phase shift keying

eNodeB Enhanced Node B (enhanced base RACH Random access channel
station) RFE Radio front end
FDD Frequency division duplexing RFPA Radio frequency power amplifier
FFT Fast Fourier transform S/P Serial-to-parallel
GMSK Gaussian minimum shift keying SAP Service access point
GT Guard time SC-FDMA Single Carrier – Frequency Division
HARQ Hybrid automatic repeat request Multiple Access

HSDPA High Speed Downlink Packet Access SNR Signal-to-noise ratio

HSUPA High Speed Uplink Packet Access STA Station

ICI Inter carrier interface TDD Time Division Duplexing

IDFT Inverse discrete Fourier transform UE User equipment

IEEE Institute of Electrical and Electronics UL Uplink
Engineers UL-SCH Uplink – shared channel
IFFT Inverse fast Fourier transform XCVR Transceiver
ISI Inter symbol interface
LO Local oscillator
LTE Long Term Evolution


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3 gpp lte physical layer

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3 gpp lte physical layer