DESIGN OF SLOTTED WAVEGUIDE ANTENNA FOR WIRELESS APPLICATION

International Research Journal of Engineering and Technology (IRJET) e-ISSN: 2395-0056
Volume: 09 Issue: 05 | May 2022 www.irjet.net p-ISSN: 2395-0072
© 2022, IRJET | Impact Factor value: 7.529 | ISO 9001:2008 Certified Journal | Page 1462
DESIGN OF SLOTTED WAVEGUIDE ANTENNA FOR WIRELESS
APPLICATION
*1 Mr. Monish Raj. D, *2Dr. Rajesh Kumar. V
*1M.Tech Student, School of Electronic Engineering (Sense), Vellore Institutions of Technology, Vellore
*2Professor, School of Electronic Engineering (Sense), Vellore Institutions of Technology, Vellore
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Abstract- Slotted waveguide antenna (SWA) arrays have
different advantages in terms of design, weight, volume,
power handling, directivity, and efficiency. For broadwall
SWAs, the slot displacements from the wall centerline
determine the antenna's side lobe level (SLL). It
demonstrates how to use a simple novel approach to
create broad wall SWAs with acceptable SLLs. Given the
needed SLL and operating frequency, this algorithm
discovers the slots length, width, locations along the
length of the waveguide, and displacements from the
centerline for a given number of identical longitudinal
slots. Because all slots have the same length and the
displacements are calculated using closed-form equations,
this approach is much easier than prior methods. A
computer programme was designed to do the design
calculations and generate the needed slots data. The
Taylor, Chebyshev, and binomial distributions are all used
in instances. In these cases, elliptical slots are employed
because their rounded corners make them more resistant
in high-power applications. The results of prototyping and
testing a SWA are consistent with the design goals..
Keywords: SWA Antenna, SLL, E-Plane, H-Plane, Bandwidth,
Displacement and co-efficiency, microwave application
1. INTRODUCTION
Rectangular Slotted Waveguide Antennas (SWAs)
transmit radiation through slots carved in the broad or
thin wall of a rectangular waveguide. As a result, the
radiating elements are integrated into the waveguide's
feed system, resulting in a simplified design that does not
require balloons or matching networks [5].SWAs also have
a low weight and small volume, as well as a high power
handling capacity, high efficiency, and an excellent
reflection coefficient. They've been perfect for numerous
radar, communications, navigation, and high-power
microwave applications because of this. Depending on
how the wave propagates inside the waveguide, SWAs can
be resonant or non-resonant., The former is a standing
wave, whereas the later is a travelling wave [6]. Although
the traveling-wave SWA has a higher bandwidth, it
requires a matching terminating load to absorb the wave
and prevent it from being reflected, reducing its efficiency.
It also has the drawback of the main beam direction being
dependent on the operating frequency. The end of the
waveguide in resonant SWAs is terminated with a short
circuit, resulting in improved efficiency due to no power
loss at the waveguide end. Furthermore, regardless of
frequency, the primary beam is normal to the array,
although these benefits come at the cost of a restricted
operation band [3].
2. Background
It demonstrated a planar SWA at 140 GHz. The
feeder SWA, which consists of a feeding slot, an overrode
cavity, and coupling slots, was developed to provide
excitations of the same amplitude but in alternating
phases. An integrated power divider and phase shifter
were used to accomplish this [4]. Coupling was also done
using longitudinal slots with the same lengths and offsets.
Kumar et al22 proposed using a planar SWA in the X-band.
The desired current distribution was synthesised using a
genetic algorithm paired with Schelkunoff's unit circle
approach. The inclined coupling slot layer and a feed layer
with a power divider were the two layers that made up the
feeder. Zhang et al.23 have demonstrated a planar SWA
that operates at 40 GHz. It was made up of five layers, with
side lobe levels suppressed using a four-corner-fed
structure with angled coupling slots. An input aperture,
feeding waveguide, and coupling slots made up the feeder.
Coburn et al24 used inclined coupling slots to feed four 8 x
8 sub array SWAs with one layer of feeding but four
separate feeding [2][3] structures to produce low sidelobe
levels for HPM applications. A planar SWA for HPM
applications was also presented by Kim et al. Radiating
slot plate, radiating waveguide, feeding waveguide, and E-
plane septum divider were the four layers of the planar. To
manage the feeding to the SWA elements, it was
additionally divided into 8 4 sub arrays, each coupled to a
multistage divider.
Our project's main goal is to create a 10 * 10
pencil-shaped SWA antenna and determine its gain, power
handling, directivity, and efficiency. Slot displacements
from the wall centerline are used to determine the
antenna's side lobe level (SLL) and to examine the antenna
radiation pattern. To find the coefficency and
displacement for related ways to compute the frequency
range, models based on Taylor and Chebyshev
distributions are utilised. A prototype SWA has been
simulated and tested, with results that are consistent with
the design.

2.1 RELATED WORK
Rashad Hassan [1] et.al. This thesis presents the
design and fabrication of a single waveguide resonator-
based aperture antenna with a 3rd order band pass filter
to demonstrate the concept. The design concept is further
improved to merge band pass filters with an aperture
antenna array based on NN waveguide resonators. This
serves to both boost the array's gain and provide filtering.
The antenna array-filter is the integrated component here.
Tarek Naous [2] et.al The design of filled SWAs was not
optimal for a specific SLR, according to the few studies
that looked into it. Based on input specifications of the
antenna's SLR, reflection coefficient, frequency of
operation, and relative permittivity of the dielectric
material, we formulate the design of dielectric-filled SWAs
as a regression problem for an accelerated design process
in the case of specified SLRs, where the developed ML
model predicts the filled SWA's design parameters with
very low error. Coburn, William [3] et. al. The array is
modular to make fabrication easier and to improve
transportability and reparability (with four symmetric
modules). The use of a rectangular waveguide corporate-
feed network reduces the antenna subsystem volume (i.e.,
depth), allowing the HPM source to be integrated into the
feed structure. An S-band array and feed structure were
built and integrated for laboratory testing. The array was
manufactured with WR-284 copper waveguide and brass
end caps to a 5-mil tolerance. The array's design,
fabrication, assembly, and testing are all taken care of. We
present preliminary test findings for one of the four
modules in the full array. The array's performance will
need to be "fine-tuned" after fabrication, as expected.
M. Al-Husseini [4] et.al. The antenna is optimised
for 3 GHz operation. The length and width of the slots are
optimised for this frequency, and their displacements are
calculated with a 20 dB sidelobe level ratio in mind. The
azimuth plane beam is then symmetrically focused and
increased by adding two rectangular metal sheets as
reflectors. Giovanni Andrea Casula [5] et.al. The T-junction
feeding the array, the effect of interaction between each
slot coupler of the feeding network and the radiating slots
closest to this coupler, and the waveguide bends are all
under consideration. When compared to the ideal
scenario, all of these effects can significantly increase the
initial sidelobes, resulting in a significant decrease in array
performance.
3. TECHNICAL SPEICIFCATION
1. Antenna Configuration
Because the desired frequency is 3 GHz, the SWA
is built using a WR-284 waveguide with a = 2.8400 and b
= 1.3700. One end of the waveguide is shorted, while the
other is fed. One of its broadsides has ten elliptical
grooves carved into it. The slots are separated half the
guide wavelength from centre to centre, with the guide
wavelength in this case being g = 138.5 mm. The slots are
arranged so that the centre of the first, Slot1, is g/4 away
from the waveguide feed and the centre of the last, Slot10,
is g/4 away from the waveguide's short-circuited side.
The waveguide's entire length is thus 5g.
The width of each slot is fixed at 5 mm, which is 2
times the ellipse's minor radius. This is determined as
follows: for X-band SWAs, the adopted width of a
rectangular slot is 0.062500, equivalent to a = 0.9 00 in
the literature. The width of the elliptical slot for this S-
band SWA is calculated from 2.8400 0.0625/0.9, which is
0.19700 or 5 mm, using proportionality. The length of the
slots (twice the major radius) is projected to be greater
than half the free space wavelength due to their elliptical
form.
The proposed method for determining the slot
displacements from the waveguide axis for a desired SLR
is described. The dimensions and guide wavelength of the
waveguide utilised in the radiating SWAs are then used to
create the feeder SWA. The radiating SWAs are eventually
placed side by side, and the feeder is connected to them.
Fig: Panel Design Structure
The three-dimensional SWA arrays in are mirrored in
their two-dimensional equivalents in the xz-plane, as
illustrated in Figure, allowing for the creation of the
proposed antenna while still offering a physical
understanding of its geometrical structure. As a result, the
proposed case's evolution is presented. The Type A
conventional antenna [9] with a wide flare-angle reflector
in Figure 5 provides an optimal gain of more than 30 dB at
the cost of a huge antenna size. The most straightforward
way to shrink the antenna's physical size is to shrink the
reflector. Unfortunately, using this method reduces
antenna gain significantly.
The slots length can be either nonuniform, in which case
the length of each slot is computed using optimization
algorithms, or uniform, in which case the length of each

slot is considered to be uniform for simplicity. Choosing
uniform slot lengths can also help you achieve your goals.
The location of the slots along the length of the SWA is
critical for keeping the slots fed in phase. The electrical
distance 2d/g2d/g, with gg being the guide wavelength
defined as the distance travelled by the electromagnetic
wave down the length of the waveguide to suffer a phase
shift of 22 radians, determines the phase shift between
consecutive slots. (2) is used to determine it, with 00
representing the free-space wavelength and c
representing the speed of light..
The waveguide operates as a transmission line by using
longitudinal slots. The TE10 mode dispersion is
symmetrical when a transverse electric field is applied to
each slot. Each slot is depicted as a shunt element using an
equivalent transmission line. When the width of the slots
is narrow[12], their offsets are not too great, and the
height of the waveguide is relatively large, this assumption
has been proven to be valid using the method of moment.
 • The antenna converts electrical energy from the
transmitter into electromagnetic energy, which is
then radiated into space; on the receiving end, the
antenna converts electromagnetic energy into
electrical energy, which is then fed into the
receiver: The fundamentals of transmit and
receive antenna operation[12]
 • Transmission - sends electromagnetic energy
into space
 In two-way communication, the same antenna can
be used for transmission and reception, thanks to
the high frequency microwave's short
wavelength, which allows for the use of highly
directional antenna. The use of a microwave
antenna for long-distance signal transmission is
more cost-effective. The use of a waveguide is
ideal for signal transmission across short
distances.
4. Metrical Method
Chebyshev Distribution at 20 dB SLR The
objective in this case is a 20 dB SLR, and the cns are
chosen using a Chebyshev distribution. Slot displacements
and coefficients The coefficients cns of a Chebyshev
distribution are determined using the following formulae.
A generalized Chebyshev array's array factor is written as:
Where:
• Tx signifies a Chebyshev polynomial of order x,
• n = cosh[cosh1(Rn)/(Nn 1)],
• u = 2(d/)(cos cos 0),
• Rn denotes the sidelobe level ratio of the nth basis
Chebyshev array, and Nn denotes the number of elements
of the nth basis array. The array factor can be stated as:
with uniform spacing and a symmetrical amplitude about
the centre
Where m equals 1 for m = 1 and equals 2 for m = 1. Finally,
the excitation coefficients are found
where:
Table: Slot displacements in radiating and feeder
SWAs for the 8 × 8 planar SWA example

First, the Feeder SWA and the eight radiating SWAs are
made. The slots were drilled with a 3 mm type carbide on
a HAAS VF-6 three axis milling machine with an accuracy
of 0.001 mm.
Coefficients and Slots Displacements
The following formulae can be used to calculate
the cns for a Taylor one-parameter distribution. For a
continuous line distribution of length l, the excitation
coefficients, In(z), are equal
to
The current magnitudes of an N-element linear array with
symmetric excitation are equivalent as in the discrete case
[12]
A 30 dB Taylor (one-parameter) taper is necessary for a
20 dB SLL for the SWA. The derived coefficients, as well as
the slot displacements.
Table −SWA SLL of 20 dB due to 30 dB Taylor (one-
parameter) coefficients and related slots
displacements.
A Taylor (one-parameter) distribution is utilised
in this example to generate a SWA SLR of 30 dB. The taper
coefficients for a 40 dB Taylor (one-parameter)
distribution are needed for this, and they're listed in Table
3 with their corresponding slots displacements. The
results demonstrate a 3 GHz antenna resonance with a
15.3 dB peak gain.
Table 3 lists the binomial coefficients and corresponding
slots displacements for the case of ten slots. The obtained
SLR is 33.5 dB, and the max gain is 15 dB for these
displacement values. The HPBW in the Y Z-plane rises to
11.1 degrees.
Table: Coefficients and corresponding slots
displacements
Measurement
A prototype SWA array was constructed and
tested to confirm the procedure presented. The waveguide
in my hand is 50 cm long. Because this length is
insufficient to accommodate 10 slots while adhering to the
various slot distance and length criteria, the design was
modified to include 7 elliptical slots. The distance between
each of these two edge slots and the adjoining waveguide
edge has been raised from g/4 to 3g/4 to avoid the two
edge slots intersecting the waveguide flanges, resulting in
a total SWA length of 4.5g. The Python computer software
that was utilised for this design allowed for this
modification. The SWA is built for a frequency of 50 kHz to
maintain the waveguide length of 50 cm. , 4.5g = 50 cm,
and g = 111.11 mm. The elliptical slot length has been
tuned to attain to this resonance frequency after the SWA
was designed with the correct uniform distribution
displacement. It is discovered to be 48 mm. The SWA was
later built to radiate with a sidelobe level of less than 20

dB using this optimised length and a slot width of 5 mm. In
this case, the excitation coefficients were calculated using
a Chebyshev distribution of 35 dB. lists these coefficients
as well as the related slot displacements.
The antenna design and a shot of the prototype
may be found here. The reflection coefficient plot provides
a comparison of two measured data and simulated results
computed using both CST and HFSS software. The antenna
had some protrusions on the corners of the elliptical slots
during Measurement 1, which were filed for Measurement
2, giving the slot a perfect elliptical form. In comparison to
the measured data, the gain patterns estimated in both
HFSS and CST are. Despite the tiny variation, which is
attributable to other fabrication flaws, a credible parallel
has been shown by inspecting the S11 and pattern figures.
5. EXPERIMENTAL RESULTS
The patch antenna is made up of three bricks: one for
the radiating plate, one for the microstrip line, and one for
the substrate, which uses CST and HFSS. A completely
electrically conducting boundary condition defines the
ground plane. Assigning coordinates is done as follows.
The ground plane and substrate begin at this point (0,0,0).
The substrate's length, L, and breadth, W, are chosen to be
28.1 mm and 32 mm, respectively. The patch's length is
0/2 12.45 mm, and its breadth is half that of the ground,
with a substrate of 16 mm. The patches, on the other hand,
begin at (28.1/4, 32/4, 0).The patch's beginning point is
14 percent of the ground plane's overall width, and it
stretches 12.45 mm in the positive x-direction. Similarly,
the patch is 14 of the total length of the ground plane in
the x-y plane (z=0) in the y-direction. Furthermore, the
feed line should be situated between the patch's starting
point and finishing point values.
Fig: SWA Design Calculation
Select File > Save As from the File menu in the Ansoft
HFSS window. Type the desired file name in the Save As
window. Select the Save button. This is how your final
model should look:
Fig: SWA Antenna
A slot antenna is made up of a metal surface having a
hole or slot carved out of it, commonly a flat plate. When a
driving frequency is used to drive the plate as an antenna,
the slot radiates electromagnetic waves in the same way
that a dipole antenna does. The radiation distribution
pattern is determined by the form and size of the slot, as
well as the driving frequency. The slots on the waveguide
will be assumed to have a narrow width. Increased width
increases bandwidth (remember that a fatter antenna
frequently has more bandwidth); nevertheless, a wider
width comes at the cost of increased cross-polarization.
Fractional Bandwidth (FBW) for thin slots can be as low as
3-5 percent, whereas FBW for large slots can be as high as
75 percent. Figure shows an example of a slotted
waveguide array (dimensions supplied by length a and
width b) slot waveguide with dimensions given by length a
and width b.
Table: Microstrip Line
it would now be simple to draw the model. You only
need to enter in the coordinates. Let's begin by sketching
the ground plane. Please refer to Table 3 for Ground Plane
coordinates. Choose Draw> Box from the menu. Enter the
box position (x, y, z) in the coordinate entry fields in Table
3, then the opposite corner of the base rectangle (dx, dy,
dz), where dx, dy, and dz stand for full length, full width,
and full height, respectively. The ground plane's
dimensions are given. When the properties dialogue box
displays, double-check that the Position, Xsize, Ysize, and
Zsize values are correct.

Select the Attribute tab and type gnd as the name's
value. Assign PEC (Perfect Electric Conductor) material to
the object by clicking on it. Then select your preferred
colour and transparency value. Select the OK option.
Let's draw the substrate next. The substrate and the
ground plane have the same dimensions. Because the
ground plane is at z = -0.794 and has no thickness (dz=0),
the substrate must be 0.794 mm thick, and since the
beginning point was zero, the complete height must be in
the -z direction. Draw > Box with the coordinates from
Table 4, set the box's location (x, y, z), and enter the box's
opposite corner (dx, dy, dz).
Coordinates are correct. Enter Substrate in the name
value box on the Attribute tab. Assign Rogers RT/Duroid
5880(tm) with a relative permittivity of 2.2 to the
material. Click OK. Select your preferred colour and
transparency value once again. Select the OK option.
Finally, make the patch. Knowing that the patch
should be in the middle, calculating the coordinates from
the ground and substrate dimensions is simple. The
patch's centre, ground plane, and substrate are all the
same size and are located at (28.1/2, 32/2, 0). To calculate
the starting point, subtract the centre point coordinates
from the substrate coordinates, and the patch's complete
length, width, and height are given. Draw > Box, your
coordinates are correct. Under the name value box, type
Patch in the Attribute tab. Assign PEC to the stuff now.
Click OK. Select your preferred colour and transparency
value once again..
RESULT AND DISCUSSION
Performance Analysis
A few characteristics, including as return loss,
bandwidth, radiation pattern, directivity, and antenna
gain, determine the performance of a designed antenna.
Fig: 2.4 GHz frequency radiation pattern.
It shows the antenna gain when phi is 90 degrees. An
antenna's gain is defined as the ratio of intensity in one
direction to the radiation intensity that would be obtained
if the antenna's power was emitted in an isotropic way.
The antenna's gain is proportional to its directivity. An
antenna's gain refers to its efficiency as well as its
directional capabilities. Gives the relationship between an
antenna's gain and directivity.
Fig: Radiation pattern in three dimensions at 2.4 GHz
In terms of SS11, far-fields E-plane and H-plane, and gain,
modelling results for the proposed array antenna 10 *10
are displayed. The array antenna's simulated resonance
frequency is 2.4 GGGGGG, with a reflection coefficient of
around 34.36 dddd. This array antenna's simulated
impedance bandwidth is around 30 MHz (2.38-2.41 GHz).
The array antenna 10 *10's simulated two-dimensional
far-fields E-plane and H-plane at 2.4 GHz. It's worth noting
that the proposed array antenna 10*10 has a very directed
emission pattern in both planes E and H. The array
antenna has also been shown to have a very high gain of
roughly 10.22 dB. Table 3 compares the performance of
the proposed array antenna with that of other array
antennas for RFID systems. The proposed array antenna
has a modest and acceptable size and a substantially
higher gain than existing reference works, as shown in the
Table.
Fig: Return loss versus. frequency for a patch antenna
operating at 2.4 GHz

Because of mismatches between the transmission
line and the feeding points, the return loss shows how
much feeding power was reflected back at the patch
antenna's port. Reflections at the antenna port move back
towards the source when the antenna and transmission
line are not exactly matched, forming a standing wave.
High return loss is required for a good antenna. The
antenna radiates best at the chosen resonance frequency,
2.4 GHz, with a return loss of 20 dB, according to from.
Bandwidth
The bandwidth of an antenna refers to the
frequency range over which it can function properly. The
antenna's bandwidth is defined as the number of Hz for
which the SLR is less than 2. The graph return loss against
frequency at point 10 dB[11] can be used to determine the
bandwidth value. The value of bandwidth is 0.28 dB, as
demonstrated in the graph of return loss against
frequency. The bandwidth restriction of various antenna
types varies.
It indicates how much power is reflected back to
the source from the antenna. The acceptable value for an
antenna is 1 VSWR 2. If the VSWR value is 1, the antenna
receives all of the power it is provided. Figure 6 shows
theFrom figure 6, the value for designed antenna is 1.
Fig: frequency plot of the patch antenna.
Fig: Simulated E and H planes at 2.40 GHz
The prototype antennas' design and a shot of the
prototype. The reflection coefficient plot compares two
measured results with simulated results computed using
both CST and HFSS software.
CST was used to replicate the planned planar SWA. Table 2
lists the computed SLR, HPBW, and gain in the E- and H-
planes, with a 3D gain pattern plot in Figure 5. As can be
seen, a pencil form pattern was achieved with an SLR of
not less than 20 dB in both planes, narrow HPBW, and is
suited for HPM applications. If the required SLR utilised to
detect the slots displacements is made larger than 20 dB,
lower sidelobe levels are easily obtained.
Table: 10*10 SWA Antenna Simulation Results
Fig: A) E-plane radiation pattern simulation (B)
element patch antenna at 2.4 GHz
Fig: For the scenario of non-uniform slots
displacements with Chebychev distribution, the
antenna's Y Z-plane pattern for 20dB

Fig: The findings of the measured and simulated
reflection coefficients were compared.
The feeder SWA is then welded to the radiating
SWAs utilising the back of the radiating SWAs' L-shaped
copper corners. Figure 6 depicts the manufactured planar
SWA. In Figure 7, the simulated gain pattern results are
compared to the measured ones. The findings of the
measured reflection coefficient are also shown.
Figure 8 shows the results of simulations using CST. As can
be observed, the measured results are extremely similar to
the simulated ones, and they are also consistent with the
design goals. This antenna array's capacity to break down
has also been investigated. On the slot responsible for the
most radiation, the maximum voltage value has been
computed. The slots in the centre of the array system give
the most radiation because they have the highest fed
power intake from the SWA feeder and the greatest
displacements from the SWA branch line centerline where
the slots are located.. The maximum voltage on these slots
is found to be 5.55 105 V/m when the system is simulated
with a high input power to the feeder SWA of 6.25 MW.
This maximum voltage is still lower than the
commencement of air breakdown, which can cause the air
to begin to break down at 3 106 V/m. If desired, a bigger
slot width value can be used to provide a lower maximum
voltage and hence a higher value of power radiated.
6. CONCLUSION
The performance parameters of the developed
SWA in this research work are shown utilizing the basic
antenna parameter characteristics of resonant frequency,
return loss (S11), VSWR, Bandwidth, Gain, Directivity, Half
Power Beam width (HPBW), and Efficiency..
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