Speed control of motor usinng matlab

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Speed control of PMBLDC motor using MATLAB/Simulink and effects of load
and inertia changes
Conference Paper · October 2010
DOI: 10.1109/ICMET.2010.5598420 · Source: IEEE Xplore
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2010 International Conference on Mechanical and Electrical Technology (ICMET 2010)
Speed Control ofPMBLDC Motor Using MATLAB/Simulink and Effects of Load
and Inertia Changes
V M Varatharaju
Research Scholar, Department of EEE,
Anna University, Chennai, INDIA,600 025,
(vmvraj@gmail.com).
B L Mathur
Professor, Department of EEE
SSN College of Engineering, Kalavakkam,
INDIA,603 110, (blmathur@ssn.edu.in)
K Udhyakumar
Assistant Professor, Department of EEE,
Anna University, Chennai, INDIA, 600 025,
(k_udhayakumar@annauniv.edu).
Abstract: Modeling and simulation of electromechanical
systems with machine drives are essential steps at the
design stage of such systems. This paper describes the
procedure of deriving a model for the brushless dc
motor with 120-degree inverter system and its validation
in the MATLAB/Simulink platform. The discussion
arrives at a closed-loop speed control, in which PI
algorithm is adopted and the position-pulse
determination is done through current control for a
standard trapezoidal BLDC motors. The simulation
results for BLDC motor drive systems confirm the
validity of the proposed method.
Keywords: PMBLDC Motor, simulation and modeling,
speed control.
I. INTRODUCTION
Recently, permanent magnet brushless dc motors
(PMBLDCM) are widely used in many applications such as
motors, sensors, actuators, etc [I]. Permanent magnet motors
with trapezoidal back EMF and sinusoidal back EMF have
several advantages over other motor types. Most notably,
(compared to dc motors) they are lower maintenance due to
the elimination of the mechanical commutator and they have
a high-power density which makes them ideal for high
torque-to weight ratio applications [2]. Compared to
induction machines, they have lower inertia allowing for
faster dynamic response to reference commands. Also, they
are more efficient due to the permanent magnets which
results in virtually zero rotor losses [3]. Permanent magnet
brushless dc (PMBLDC) motors could become serious
competitors to the induction motor for servo applications.
The PMBLDC motor is becoming popular in various
applications because of its high efficiency, high power factor,
high torque, simple control and lower maintenance [4]. The
major disadvantage with permanent magnet motors is their
higher cost and relatively higher complexity introduced by
the power electronic converter used to drive them. The added
complexity is evident in the development of a torque/speed
regulator [5]. The magnetization directions and intensities
978-1-4244-8102-6/10/$26.00 CO 2010 IEEE 543
are analyzed using finite element analysis with a detailed
magnetization procedure for ferrite bonded magnets used in
inner-rotor type BLDC motors [6]. The effect of stator
resistance on average-value modeling of electromechanical
systems consisting of BLDC motor and 120-degree inverter
systems, including commutation current has been presented
[7]. It is shown that the model becomes more accurate both
in time and frequency domains for the motors with large
stator resistance (small electrical time constant of the stator
winding) typically operate with small commutation angle.
Bhim singh, B P singh and K Jain have proposed a digital
speed controller for BLDCM and implemented in a digital
signal processor [8]. Later in 1998 peter vas has developed
scheme to extract the rotor position and the speed of BLDC
motor by Extended Kalman Filter (EKF) [9]. MJadric and
B. Terzic have successfully adapted the Hall Effect sensor to
sense the rotor position for every 60 degree electrical [10].
Due to the extensive use of modeling and simulation and
the heavy reliance on their accuracy, both simulation speed
and model accuracy are very important. For the purposes of
stability analysis and controller design, it is often desirable to
investigate the large-signal transients and small-signal
characteristics of the system. Simulation studies are also
often performed many times to achieve the required design
goals. In this study, the nonlinear simulation model of the
BLDC motors drive system with proportional-integral (PI)
control based on MATLAB/Simulink platform is presented.
The simulated results in terms of electromagnetic torque and
rotor speed are given.
II. NARRATIVE OF PMBLDCM DRIVE
Fig.1 shows the typical BLDC motor controlled by an
inverter. Typical Hall-sensor-controlled BLDC motors, such
as the one considered in this paper, is very common. The
inverter converts a dc source voltage into 3-phase ac voltages
with frequency corresponding to the rotor position and speed.
This paper focuses on typical Hall-sensor controlled VSI
driven BLDC motors, where the inverter operates using 120-
degree commutation method. Rotor position is sensed by
Hall Effect sensors embedded into the stator which gives the
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sequence of phases. Whenever the rotor magnetic poles pass
near the Hall sensors, they give a high/low signal, indicating
the N or S pole is passing near the sensors. The three Hall
sensors, HI, m, and H3, are used to detect the rotor position.
To rotate the BLDC motor, the stator windings should be
energized in a sequence. Based on the combination of these
three Hall sensor signals, the exact sequence of commutation
can be determined
A
B
c
Hall
sensor outputs
bs-axis
as
Figure 1. BLOC Motor controlled by the inverter
A. Closed Loop Control
Fig.2 describes the basic building blocks of the
PMBLDCM drive system. The drive consists of speed
controller, reference current generator, pulse width
modulation (PWM) current controller, position sensor, the
motor and a IGBT based voltage source inverter (CC-VSI).
The speed of the motor is compared with its reference value
and the speed error is processed in PI speed controller. The
output of this controller is considered as the reference torque.
A limit is put on the speed controller output depending on
permissible maximum winding currents. The reference
current generator block generates the three phase reference
currents (ia*, ib*, ic*) using the limited peak current
magnitude decided by the controller and the position sensor.
The PWM current controller regulates the winding currents
(ia, ib, ic) within the small band around the reference
currents(ia*, ib*, ic*)' The motor currents are compared with
the reference currents and the switching commands are
generated to drive the power switches.
544
Figure 2. PMBLDC motor drive system
The PI controller is widely used in industry due to its
ease in design and simple structure. The rotor speed cor(n) is
compared with the reference speed corCn)* and the resulting
error is estimated at the nth sampling instant as:
lVe(n) = lVr(n) *-lVr(n) (1)
The new value of torque reference is given by
T (n) = T (n -1) + KplVe(n) -lVe(n -1) + KIlVe(n) (2)
Where, 'coe(n-I), is the speed error of previous interval,
and 'co.(n)' is the speed error of the working interval. Kp and
K, are the gains of proportional and integral controllers
respectively. By using Ziegler Nichols method the Kp and K,
values are determined [11].
B. Reference Current Generator
The magnitude of the reference current (1*) is determined by
using reference torque (T*) and the back emf constant (Kb);
* r*
I = - [12]. Depending on the rotor position, the
Kb
reference current generator block generates three-phase
reference currents (ia*, ib*, ic*) considering the value of
reference current magnitude as 1*, - 1* and zero. The
reference current generation is explained in the Table.I.
Table I.Rotor position signal Vs reference current
Rotor Position Signal Reference Currents
Or
(ia*, ib*, ic*
)
eo _ 60° 1* -1* 0
60° - 120° 1* 0 -1*
120° -180° 0 1* -1*
180° - 240° -1* 1* 0
240° - 300° -1* 0 1*
300° - 360° 0 -1* 1*

C. PWM Current Controller
The PWM current controller contributes to the generation
of the switching signals for the inverter switches. The
switching logic is formulated as given below.
If ia < (ia*) switch 1 ON and switch 4 OFF
If ia> (ia*) switch 1 OFF and switch 4 ON
If ib < (ib*) switch 3 ON and switch 6 OFF
If ib> (ib*) switch 3 OFF and switch 6 ON
If ie < (i/) switch 5 ON and switch 2 OFF
If ie> (ie*) switch 5 OFF and switch 2 ON
III. MODELING
A. BackEMF
The phase back emf in the PMBLDC motor is trapezoidal
in nature and also a function of the speed (cor) and rotor
position angle (er) as shown in Fig.3.
Figure 3. Components ofback EMF
The normalized function of back emfs is shown in Fig.5.
From this, the phase back emf ean can be expressed as
fa (Or) =E
fa (Or) =(6E /1<)(1< -Orr)- E
fa (Or) =-E
fa (Or) =(6E /1<)(O,r - 21<) + E
00< 0,< 1200
1200< Or< 1800 (3)
1800< Or< 3000
3000< Or< 3600
Where, E=Kb(()r and ean can be described by E and
normalized back emf function fier) [ean = E fa(Or)] .
The back emf functions of other two phases (ebn and ecn) can
also be determined in similar way using E and the
normalized back emf function fb(er) and fe(er).
IV. PMBLDC MOTOR AND INVERTER
The PMBLDC motor is modeled in the 3-phase abc
frame. The general volt-ampere equation for the circuit
shown in the FigA can be expressed as:
545
Van = Ri a + PAa + e a
n
Vbn =Rib + PAb + ebn
Vcn =Ric+pAc+ecn
(4)
(5)
(6)
Where, Van. Vbn and Ven are phase voltages and may be
defined as:
Vdc
Figure 4. Inverter circuit with PMBLDCM drive
Van =
Vao - Vno'
Vbn =
VbO - VnO' and
Vco =
Vco - Vno.
(7)
Where VaO, VbO, VeO and VnO are three phase and neutral
voltages with respect to the zero reference potential at the
mid-point of dc link (0) shown in the FigA. R is the
resistance per phase of the stator winding, p is the time
differential operator, and ean, �n and ecn are phase to neutral
back emfs. The A.a, Ab and Ac are total flux linkage of phase
windings a, b and c respectively. Their values can be
expressed as:
Aa = LSia - M(ib + iJ (8)
Ab = Lsib -MUa + U (9)
(10)
Where, 'Ls' and 'M' are self and mutual inductances
respectively.
The PMBLDC motor has no neutral connection and
hence this results in,
ia + ib + ic = 0 (11)
Substituting (11) in (8), (9) and (10), the flux linkages are
obtained.
Aa = ia(Ls + M),
Ab = ib(Ls + M),and
Ae = ie(Ls + M)
(12)
By substituting (12) in volt-ampere relations (4)-(6) and
rearranging these equations in a current derivative of
statespace form, gives,
pia = lI(Ls + M)(Van - Ri a - ean)
pib = lI(Ls + M)(Vbn - Rib - ebn)
(13)
(14)

as
pic = lI(Ls +M)(Vcn-Ri c-ecn) (15)
The developed electromagnetic torque may be expressed
Te =(eania+ ebnib+ ecnic)/ w, (16)
Where, 'ro/ is the rotor speed in electrical rad/sec.
Substituting the back emfs in normalized form, the
developed torque is given by
T, = K {fa(8r)ia + fb(8r)ib + fc(8r)ic} (17)
The mechanical equation of motion in speed derivative
form can be expressed as:
pw, = (P / 2)(Te - TL -Bwr) / J (18)
Where, 'P' is the number of poles, 'TL' is the load torque
in N-m, 'B' is the frictional coefficient in Nm/rad, and '1' is
the moment of inertia in kg_m2•
The derivative of the rotor position (9r) in state space
form is expressed as:
pO, = w, (19)
The potential of the neutral point with respect to the zero
potential (vno) is required to be interpreted properly to avoid
the imbalance in applied phase voltages.
This can be obtained by substituting (7) in (4) to (6) and
adding them together to give
VaO +VbO +Vco -3VnO = R(ia+ ib+ ic)+ (20)
(Ls +M)(pia+ pib+ pic)+(ean+ ebn+ ecn)
Substituting (11) in (20) results in
VaO +�o +v"o -3v"o = (ean +ebn +ecn)
� v"o = [VaO +�o +v"o -(ean +ebn +ecJ]/3
(21)
The set of differential equations viz. (13),(14), (15), (18)
and (19) defines the developed model in terms of the
variables ia, ib, ie, ron and 9r for the independent variable, time.
V. SIMULATION RESULTS
In this work the drive model with PI speed controller is
developed and simulated in order to validate the model and
the designed controller. For conducting the studies and
analysis, this paper considers a typical industrial BLDC
motor (Arrow Precision Motor Co., LTD) with importance
specifications: 2hp, I500rpm, 4 poles (Refer Appendix).
Fig.5-I2 shows simulated results.
$...dy $,••• C........n'
Figure 5. Stator phase currents
546
Back El1F or the BLDC motor
,0011 ' n n n ' 1 ' n n n j
t .,��
I Eb
1 '�
�
� 100
E<
Figure 6. Trapezoidal back EMF
,1&·.:T�i··.·;".l�1··.··,;,···.r::rr�···.I···.;,r�i·.·;".�
'::
�o 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1
Figure 7. Reference current waveform
Output Pha.. voltage (Van)
Figure 8. Representative phase voltage (van)
Fig.5 and Fig.6 show the stator phase currents and back
emf respectively. Fig.7 shows the reference current. The
typical phase voltage is diagrammed in Fig.8. Fig.9 shows
the torque and the speed variations, and the motor speed
quickly converges to the reference shortly after startup and
recovers very well from the load torque disturbance as well
as parameters variation. The moment of inertia value taken
for this case is 0.013kg-m2 and it reaches the steady state
torque and speed suddenly at time 0.03seconds.When the
moment of inertia is increased to 0.098kg-m2 it takes 0.28
seconds to reach the steady state as evidenced in Fig.II.
From the figure, it is inferred that increasing the moment of
inertia will cause the settling time to increase.
Fig.10 and Fig.12 demonstrate the drive performance
with step inertia change. The simulated results show that
synchronization of the rotor speed is well done and the
average electromagnetic torque is in equilibrium although
the dynamic electromagnetic torque is not in equilibrium

l : i ; ; • : ! ; : l
Time(nu)
i1: : : : : : : : : .
o 0.9 1
Tim�(IItI)
Figure 9. Torque and speed responses during startup transients
!�l. , : : I ; , , • 1
Timell)
'1[ :, : I. ,�" .� .� :. 1
Time(I)
Figure 10. Torque and speed responses - step input change - moment of
inertia 0.013 kg-m2 (step time 0.5 S)
t JCT :l Ii . 11 .1
I o
L.t::::t : 1 ' . : : : _
l ,o°VtI
··· · ,
.
...... iii iii j
�
50
· : - : : [ : ! [
o �.... :. .... . . :..
.
.. . .:... . ... : .. .....:... . ... :. . . . . .
_
o 0.1 0,2 0.3 0.4 0.5 0.6 0.7 O.B 0.9 1
Tirne(sec) �
Figure 1L Torque and speed responses at moment of inertia 0.098 kg-m
'
'::N=
··· ·�I ' '······��··i········,'dJ
'
t °r······:�······· : r:l·�:T':�"'·�·'·'::·f:···::i
·50 '----
�
-
-'--
-
-"--
---'
-
�
-
�
-
"----
----'-
-
-'--
-----'
1,50 .. .. .. ' � : ' �
i ':V±tr F+J , ! j
o
0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1
Tim.,(sec) �
Figure 12. Torque and speed-Step input with moment of inertia 0.098
kg-m2 (step time 0.5 S)
547
Figure 13. Step load torque (9Nm) at 0.75 step
Figure 14. Step load torque (25 Nm) at 0.75
:��
V�-1�- .-�] -�l-��[--l-��[�-.--��.
40 ......... ............: . . .. . . . ... :. ... . . . .. . :. ... . . . .. . :. .. . . . . .. . ;. .. . . . ... . :.
. . . . .. . . . : . . . . .. . . . : . . . . .. . .
20 l j '•.........i ............: : '......................
.
.
o .. ......, ............ .. .. ..... ............ ....... .... . ,... .. ..... , .. .. . .... ....... . .. . ..... .... . ... . .. .....
. . . . . . . . .
Figure 15. Application of heavy load (100 Nm)
Figures 13 to 16 show the performance while load
changes. The results demonstrate that the designed PI
controller is triumph in restoring the steady state. Fig.15
exhibits that iIf the load torque is increased into 100 Nm then
the actual speed decreases into 48 RPS.
]tffi
��
im �
�
J••••••••••••••••••••••••••.�
100 .... ... ..,........ . . , . .......... ....:.... . . ......... . . .,.........., .... . .. .. ....'
150 vy
'
.
·
.
•. ..�
..•'.•. :
:=u. . . . . . •. . . . . . . . . . !==. . . . •. . . . . . . . . . •. . . . . . . . .
o m � � U M M V M M 1
Figure 16. Load toque 25Nm at step of 0.5

VI. CONCLUSION
The nonlinear simulation model of the BLDC motors
drive system with PI control based on MATLAB/Simulink
platform is presented. The control structure has an inner
current closed-loop and an outer-speed loop to govern the
current. The speed controller regulates the rotor movement
by varying the frequency of the pulse based on signal
feedback from the Hall sensors. The performance of the
developed PI algorithm based speed controller of the drive
has revealed that the algorithm devises the behavior of the
PMBLDC motor drive system work satisfactorily. Current is
regulated within band by the hysteresis current regulator.
And also by varying the moment of inertia observe that
increase in moment of inertia it increases simulation time to
reach the steady state value.
Consequently, the developed controller has robust speed
characteristics against parameters and inertia variations.
Therefore, it can be adapted speed control for high
performance BLDC motor.
REFERENCES
[I] Duane C.Hanselman, "Brushless Permanent-Magnet Motor Design",
McGraw-Hill, Inc., New York, 1994.
[2] TJ.E.Miller, 'Brushless Permanent Magnet and Reluctance Motor
Drives.' Oxford Science Publication, UK, 1989.
[3] RKrishnan, Electric Motor Drives: Modeling, Analysis, and Control,
Prentice-Hall, Upper Saddle River, NJ, 2001.
[4] P Pillay and R Krishnan, "Modeling, simulation, and analysis of
permanent Magnet motor drives. Part II: The brushless dc motor
drive," IEEE Transactions on IndustryApplications, vol.IA-25, no.2,
pp.274-279, Mar./Apr. 1989.
548
[5] RKrishnan and A.J. Beutler, "Performance and design of an axial
field permanent magnet synchronous motor servo drive,"
Proceedings ofIEEE lASAnnual Meeting, pp.634-640,1985.
[6] In-Soung Jung.Ha-Gyeong Sung, Yon-Do Chun, and Jin-Hwan Borm,
"Magnetization Modeling of a BondedMagnet for Performance
Calculation of Inner- Rotor Type BLDC Motor", IEEE Transactions
on Magnetics, voU7, no.4, pp.2810-2813, July 2001.
[7] Qiang Han, Hee-Sang Ko, Juri Jatskevich, ''Effect of Stator Resistance
on Average-Value Modeling of BLOC Motor 120-Degree Inverter
Systems", Proceeding of International Coriference on Electrical
Machines and Systems pp.481-486, Oct. 8-11, Seoul, Korea, 2007.
[8] Bhim singh, B P Singh and (Ms) K Jain," "Implementation of DSP
Based "Digital Speed Controller for Permanent Magnet Brushless dc
Motor" Proceedings of IE(I) Journal-EL, 2002.
[9] M.Lajoie-Mazenc, C.Villanueva, and J.Hector, "Study and
implementation of a hysteresis controlled inverter on a permanent
magnet synchronous machine," IEEE Transactions on Industry
Applications, vol. IA-21, no.2, pp.408-413, March/April 1985.
[10] TSebastian and G.RSlemon, "Transient Modeling and Performance
of Variable Speed Permanent Magnet Motors." IEEE Transactions on
lA, vol-25, no.l, pp.101, January/February 1989.
[II] A.Rubai and RC.Yalamanchi, "Dynamic Study of an Electronically
Brushless dc Machine via Computer Simulations." IEEE
Transactions on EC, vol-7, no.l, pp.132, March 1992,
[12] P.C.K.Luk and C.K.Lee, "Efficient Modeling for a Brushless dc
Motor Drive", Coriference Record ofIEEE-IECON, pp.188, 1994.
Rating:
Number of Poles:
Type of connection:
Rated speed:
Rated current:
Resistance/phase:
Back EMF constant:
Inductance (L, + M):
Moment of Inertia:
4
Star
2.80
APPENDIX
2.0 hp
1500 rpm
4A
1.23V sec/rad
0.00521 H/phase
0.013 Kg-m
2
/O.098 kg _m
2
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