Implementation on the dSPACE 1104 of VOC-SVM based anti-windup PI Controller of a three-phase PWM rectifier

International Journal of Power Electronics and Drive Systems (IJPEDS)
Vol. 12, No. 3, September 2021, pp. 1586~1597
ISSN: 2088-8694, DOI: 10.11591/ijpeds.v12.i3.pp1586-1597  1586
Journal homepage: http://ijpeds.iaescore.com
Implementation on the dSPACE 1104 of VOC-SVM based anti-
windup PI Controller of a three-phase PWM rectifier
J. Lamterkati1
, L. Ouboubker2
, M. Khafallah3
, A. El afia4
1
RITM Laboratory, Higher School of Technology, Casablanca (ESTC), Morocco
1,2,3,4
Energy and Electrical Systems Laboratory, ENSEM, Hassan II University, Casablanca, Morocco
2
LGEMS Laboratory, ENSA-Agadir, Ibn Zohr University, Agadir, Morocco
4
ENSAM, Hassan II University, Casablanca, Morocco
Article Info ABSTRACT
Article history:
Received Dec 29, 2020
Revised Jun 27, 2021
Accepted Jul 2, 2021
The study made in this paper concerns the use of the voltage-oriented control
(VOC) of three-phase pulse width modulation (PWM) rectifier with constant
switching frequency. This control method, called voltage-oriented control
with space vector modulation (VOC-SVM). The proposed control scheme
has been founded on the transformation between stationary (α-β) and and
synchronously rotating (d-q) coordinate system, it is based on two cascaded
control loops so that a fast inner loop controls the grid current and an
external loop DC-link voltage, while the DC-bus voltage is maintained at the
desired level and ansured the unity power factor operation. So, the stable
state performance and robustness against the load’s disturbance of PWM
rectifiers are boths improved. The proposed scheme has been implemented
and simulated in MATLAB/Simulink environment. The control system of the
VOC-SVM strategy has been built based on dSPACE system with DS1104
controller board. The results obtained show the validity of the model and its
control method. Compared with the conventional SPWM method, the VOC-
SVM ensures high performance and fast transient response.
Keywords:
Anti-windup PI controller
dSPACE 1104
Space vector modulation
Three-phase PWM rectifier
Voltage oriented control
This is an open access article under the CC BY-SA license.
Corresponding Author:
Jawad Lamterkati
Departement of Electrical Engineering
Hassan II, University
Higher School of Technology (ESTC), Casablanca, Morocoo
Email: jawad.lamterkati@gmail.com
1. INTRODUCTION
The use of high-power electronics is being extended to different system related to power generation,
industrial equipements, traction applications. Unfortunately, the standar diode/thyristor bridge rectifiers at the
input side cause several problems as: Low power factor, high values of harmonic distortion of a line current
and harmonic pollution on the grid, uncontrolled DC-link output voltage and the power flow unidirectionnel.
So, new generation of controlled rectifiers has been investigated know as three-phase voltage source PWM
rectifiers. The PWM rectifier is a preferred choise for providing a DC loads or voltage source fed drives, due
to its capability of DC voltage control and bi-directional power flow, input power factor regulation, line
current harmonic reduction [1], [2].
For improving the input power factor and shaping the input current into sinusoidal waveform,
various control algorithms for PWM rectifier have been proposed in recent researchses which can be
subdivised in to two groups according to their use of current control loop or active/reactive power control
loop [3]-[9]: The voltage-oriented control (VOC), virtual flux-oriented control (VFOC), the voltage based

Int J Pow Elec & Dri Syst ISSN: 2088-8694 
Implementation on the dSPACE 1104 of VOC-SVM based anti-windup PI … (J. Lamterkati)
1587
direct power control (V-DPC) and virtual flux based direct power control (VF-DPC). A wellknow algorithm
among indirect power control that uses current controller is the method that is called voltage-oriented control
(VOC), it’s similar to the field-oriented control (FOC) of the induction motor, where the VOC method is able
to produce high dynamic and static performance throuph the usage of internal current control loops and an
outer voltage control loop. VOC is based on the rotating synchronous reference frame orientation with
respect to the grid line voltage vector. By transforming the three phase quantities to appropriate DC
components, the proportional and integral (PI) controllers are able to lead to estimated dq components to the
desired reference values with zero steady state error [8]-[12]. The d-axis reference current is controlled to
perform the DC-link voltage regulation while the reference current in q-axis is controlled to obtain a unity
power factor [13].
Many different PWM modulation schemes are being used, such as sinusoidal PWM, delta
modulation techniques and the space vecteur technique. It has been analyzed theorically and proved that the
SVM technique is the best modulation solution on the whole. SVM is the best way to suppress the input
harmonic as well for specific applications such as motor speed control. Another advantage of using SVM
technique in inverter can achieve 15% more fundamental component in the output voltage and provides 33%
reduction of effective switching frequency. However, switching losses also strongly depend on a load power
factor. It is very important criterion, which allows farther reduction of switching losses up to 50% [14].
Finally, the proposed VOC-SVM technique was tested both in simulation and experimentally, using dSPACE
1104-based experimental prototype, and illustrative results are presented. Results confirm the effectiveness
and the high performance of the proposed VOC.
2. WORKING PRINCIPLES AND MODELING OF THREE-PHASE PWM RECTIFIER
The circuit diagram of the three-phase voltage source rectifier structure is shown in Figure 1. In
order to set up math model, it is assumed that the AC voltage is a balanced three-phase supply, the filter
reactor is linear, IGBT is ideal switch and lossless [15], [16]. The converter is connected to the three-phase
power supply via an inductor L and internal resistance R for each phase. The three-phase voltage supply is
denoted ea, eb and ec. Three identical line inductors indicated by La, Lb and Lc act as line filters for smoothing
the line current with minimum ripples. Each inductor has an internal resistance which is denoted by Ra, Rb
and Rc. A part of reducing the total harmonic distortion (THD) of the line currents, the inductions also
provide the boost the feature of the converter. Six power transistors (IGBTs) with anti-parallel diode are used
as the SVR power switches, since, IGBTs have features of high-power rating which is used to carry out the
PWM generation as well as the power bidirectional conversion, a load and capacity are connected
simultaneously at the output of the converter. The capacity is used as a voltage source and follows the
rectifier to also operate as an inverter [17].
The state of switches in each of the leg can be described using switching function defined in (1).
𝑆𝑘(𝑡) = {0,1}, 𝑘 = 𝑎, 𝑏, 𝑐 (1)
There are six actives’ states of converter for 𝑆𝑎 + 𝑆𝑏 + 𝑆𝑐 = {1,2} and two passive states for 𝑆𝑎 +
𝑆𝑏 + 𝑆𝑐 = {0,3}. In each of the active state there exists a circuit for energy transfer between the DC and AC
side.
The voltage equations are given by:
{
𝑒𝑎 = 𝐿
𝑑𝑖𝑎
𝑑𝑡
+ 𝑅𝑖𝑎 + 𝑣𝑎
𝑒𝑏 = 𝐿
𝑑𝑖𝑏
𝑑𝑡
+ 𝑅𝑖𝑏 + 𝑣𝑏
𝑒𝑐 = 𝐿
𝑑𝑖𝑐
𝑑𝑡
+ 𝑅𝑖𝑐 + 𝑣𝑐
(2)
The current across C is:
𝐶
𝑑𝑣𝑑𝑐
𝑑𝑡
= 𝑆𝑎𝑖𝑎 + 𝑆𝑏𝑖𝑏 + 𝑆𝑐𝑖𝑐 − 𝑖𝐿 (3)
The (2) can be rewritten as following:

 ISSN: 2088-8694
Int J Pow Elec & Dri Syst, Vol. 12, No. 3, September 2021 : 1586 – 1597
1588
{
𝐿
𝑑𝑖𝑑
𝑑𝑡
= 𝑒𝑑 − 𝑅𝑖𝑑 + 𝜔𝐿𝑖𝑞 − 𝑣𝑑
𝐿
𝑑𝑖𝑞
𝑑𝑡
= 𝑒𝑞 − 𝑅𝑖𝑞 − 𝜔𝐿𝑖𝑑 − 𝑣𝑞
𝐶
𝑑𝑣𝑑𝑐
𝑑𝑡
=
3
2
(𝑆𝑑𝑖𝑑 + 𝑆𝑞𝑖𝑞) −
𝑣𝑑𝑐
𝑅𝐿
(4)
3. VOLTAGE ORIENTED CONTROL TECHNIQUE (VOC)
The voltage-oriented control (VOC) strategy is based on the knowledge of the position of the line
voltage vector and the relative spatial orientation of the current vector. Typically, grid connected converters
control-structures are based on Park’s transformation to a rotating (d-q) reference frame (aligned with the
line-voltage). In fact, it is usually built by two cascaded control loops so that a fast-inner loop controls the
grid current and an external loop the DC-link voltage. The control structure of the proposed scheme is shown
in Figure 1.
Figure 1. Structure of voltage oriented control in a rotating synchronous reference frame
It given in the synchronous (d-q) coordinates:
𝑝 = (𝑒𝑞𝑖𝑞 + 𝑒𝑑𝑖𝑑) =
3
2
𝐸𝑚𝐼𝑚
𝑞 = (𝑒𝑞𝑖𝑑 − 𝑒𝑑𝑖𝑞) (5)
Different control strategies have been proposed for this three-phase boost operation [17], [18]. If
iq=0 and eq=0 the active and reactive power equations will be simplified to 𝑝 =
3
2
𝐸𝑚𝐼𝑚 and q=0. Based on
these equations, the feedforward current control method is one of the widely used schemes for power control.
Figure 3 shows the basic diagram of the controller. The dq current control and feedforward compensation are
the main parts of this decoupled control scheme. The controller has an outer loop for the DC-bus voltage

1589
regulation. This controller output sets the reference value for the d component of the current that controls the
power [19].
− Current decoupling control of three-phase voltage source PWM rectifier
It is clear from (9) that the converter equations in the (d-q) axis are coupled to to each other through
Lwiq and Lwid terms, which means that if we control one of them, the other one will be changed
correspondingly, thus we can not control them independently. So, we need to carry on the decoupling control
in the order to control them independently. We use the strategy of feed-forward decoupling control, make:
{
𝐿
𝑑𝑖𝑑
𝑑𝑡
+ 𝑅𝑖𝑑 = (𝑘𝑝 +
𝑘𝑖
𝑠
) ∗ (𝑖𝑑𝑟𝑒𝑓 − 𝑖𝑑)
𝐿
𝑑𝑖𝑞
𝑑𝑡
+ 𝑅𝑖𝑞 = (𝑘𝑝 +
𝑘𝑖
𝑠
) ∗ (𝑖𝑞𝑟𝑒𝑓 − 𝑖𝑞)
(6)
Substitute (6) into (5):
{
𝑣𝑑 = (𝑘𝑝 +
𝑘𝑖
𝑠
) ∗ (𝑖𝑑𝑟𝑒𝑓 − 𝑖𝑑) − 𝜔𝐿𝑖𝑞 + 𝑒𝑑
𝑣𝑞 = (𝑘𝑝 +
𝑘𝑖
𝑠
) ∗ (𝑖𝑞𝑟𝑒𝑓 − 𝑖𝑞) + 𝜔𝐿𝑖𝑑 + 𝑒𝑞
(7)
Substitute (7) in (4):
{
𝑑𝑖𝑑
𝑑𝑡
=
1
𝐿
(𝑘𝑝 +
𝑘𝑖
𝑠
) ∗ 𝑖𝑑𝑟𝑒𝑓 −
1
𝐿
[𝑅 + (𝑘𝑝 +
𝑘𝑖
𝑠
)] ∗ 𝑖𝑑
𝑑𝑖𝑞
𝑑𝑡
=
1
𝐿
(𝑘𝑝 +
𝑘𝑖
𝑠
) ∗ 𝑖𝑞𝑟𝑒𝑓 −
1
𝐿
[𝑅 + (𝑘𝑝 +
𝑘𝑖
𝑠
)] ∗ 𝑖𝑞
(8)
After decoupling control (8) we can control id and iq independently, thus we can resperctively
control the active and reactive powers independently and this can make de design of current loop mush
easier. Current loop design block diagram is shown in Figure 3. In order to design the voltage loop, the
reactive compoment be zero to insure the PWM rectifier uinity power factor [20]-[22]. The given value of
active compenent id is produced by anti-windup PI controller, which shonw in (9), the kp is the proportionly
factor, the ki is the integral coefficient.
𝑖𝑑𝑟𝑒𝑓 = (𝑘𝑝 +
𝑘𝑖
𝑠
)(𝑉𝑑𝑐,𝑟𝑒𝑓 − 𝑉𝑑𝑐) (9)
Figure 2. Structure diagram of currents decoupling

 ISSN: 2088-8694
1590
4. SYNTESIS OF CONTROLLERS
4.1. Design of current controller
The block diagram of current control loop is shown in Figure 4; basically, they tend to regulate the
active and reactive current respectively. The d-axis current loop attempts to maintain a constant DC voltage
by tracing the reference current value id,ref produced by the outher voltage loop. In order to achieve the unity
power condition, the q-axis current component iq,ref has to be set to zero [14].
Figure 3. Current control loop diagram
The line voltage is seen as a constant perturbation, and is compensated by the integral part of PI controller.
In this way, the zero of the PI controllers is placed over the pole of the system. So:
𝑇𝑖 =
𝐿
𝑅
(10)
With this synthesis, in closed-loop, the system will be simplified and its closed loop transfer function is:
𝐹(𝑠) =
1
1+𝑠𝑇𝑖𝑅
(11)
The close-loop time constant 𝑇𝑐 = 𝑇𝑖𝑅 can be a specification of the controller design. So:
𝑇𝑖 =
𝑇𝑐
𝑅
(12)
The parameters of the current loop PI controller can be given by:
𝑘𝑖𝑝 =
𝑇𝑛
𝑇𝑖
=
𝐿
𝑇𝑐
and 𝑘𝑖𝑖 =
1
𝑇𝑖
=
𝑅
𝑇𝑐
(13)
The active and reactive current control loops are similar; there-fore, the (13) is valid for both controllers.
4.2. Design of voltage controller
After correction, the current loop is considered to be equal to unity. Thus, the block diagram of
voltage control loop is given in Figure 5. In order to limit DC bus voltage fluctuations a proportional-integral
(PI) controller with anti-windup compensation is proposed for the DC bus regulation. The regulator acts
using a proportional gain Kp, improving the dynamic and the quantity of intergrator via the gain Ki, for good
operation in steady sate [23].
To limit the saturation of the output of the controller, caused by noise detection amplification, an
anti-windup loop is added by a second integrator term, with a loop gain (1/Tu) chosen to high, without
affecting the desired performances [24], [25]. Taking into account the PI regulateur function transfer function
and that of the DC side, the synthesis of the Kp and Ki gains of the PI controller passes through placement of
the poles of direct closed loop, is given by the following transfer function:
𝑉𝑑𝑐
𝑉𝑑𝑐,𝑟𝑒𝑓
=
𝑘𝑝.𝑠+𝑘𝑖
𝐶.𝑠2+𝑘𝑝.𝑠+𝑘𝑖
=
𝑘𝑝/𝐶(𝑠+𝑘𝑖/𝑘𝑝)
𝑠2+𝑘𝑝/𝐶.𝑠+𝑘𝑖/𝐶
(14)
From (11), we note that the closed loop is a canonical transfer function of second order:
𝑉𝑑𝑐
𝑉𝑑𝑐,𝑟𝑒𝑓
=
𝜔𝑛
2
𝑠2+2.𝜉.𝜔𝑛.𝑠+𝜔𝑛
(15)

1591
By equalizing (14) and (15), and adopting an optimal damping coefficient; the gains of controller
are quantified as follows:
𝑘𝑝 = 2. 𝜉. 𝜔𝑛. 𝐶 and 𝑘𝑖 = 𝐶. 𝜔𝑛
2
(16)
Figure 4. Anti-windup PI controller for DC-link voltage control
5. SPACE VECTOR MODULATION TECHNIQUE
The space vector modulation (SVM) is an alternative inverter switch control method to conventional
sinusoidal PWM, it is characterized by a fast-transient response and a less harmonic distortion [26]. Control
structure is greatly simplified and power electronic hardware is exploited to the maximum. The voltage
vectors which are generated by the inverter for each sampling period are plotted in Figure 5. There are eight
possible ouput voltage vectors, six active vectors V1-V6, and two zero vectors V0-V7 correspond to the inverter
switches states S0(000), S1(100), …, S7(111), respectively.
The principle of SVM is the prediction of inverter voltage vector by the projection of the reference
between adjacent vectors in each sector Ni: (𝑖 − 1)
𝜋
3
< 𝑆𝑖 ≤ 𝑖
𝜋
3
. The determination of the sector is based on
the following expression:
𝜃𝑠 = 𝑎𝑟𝑐𝑡𝑎𝑛 (
𝑉𝑠𝛽
𝑉𝑠𝛼
) (17)
where 𝑉
𝑠𝛼 and 𝑉𝑠𝛽 denote the voltage vector components in the Concordia reference.
The principle of the SVM’s is to project the desired voltage vector Vsref on two adjacent voltage
vectors Vi and Vi+1 corresponding to two switching states of the inverter. The values of this projection
provide the determination of desired commutation times Ti and Ti+1 and correspond to two nonzero switching
states of the inverter. To maintain the constant commutation frequency, in the case where Ti+Ti+1≤TPWM, a
zero state of the inverter is applied during a complementary duration to the period TPWM.
When the reference voltage vector Vsref is in sector 1 (Figure 5), it can compose by the active voltage
vectors V1, V2 and V0 [27], [28]. For a cycle switching, we have:
𝑉
⃗𝑠𝑟𝑒𝑓 = 𝑉
𝑠𝛼 + 𝑗𝑉𝑠𝛽 =
𝑇1
𝑇𝑃𝑊𝑀
𝑉
⃗1 +
𝑇2
𝑇𝑃𝑊𝑀
𝑉
⃗2 (18)
Where:
𝑇𝑃𝑊𝑀 = 𝑇1 + 𝑇2 + 𝑇0 (19)
The inclusion of zero basic vectors does’nt affect the vector sum Vsref, it only helps to balance the turn on and
off periods of the transistors, and thus their power dissipation. The expressions of the voltage vector are:
{
𝑉
⃗1 = √
2
3
𝐸(𝑐𝑜𝑠 0 + 𝑗 𝑠𝑖𝑛 0)
𝑉
⃗2 = √
2
3
𝐸 (𝑐𝑜𝑠
𝜋
3
+ 𝑗 𝑠𝑖𝑛
𝜋
3
)
(20)

 ISSN: 2088-8694
1592
The expression of T1 and T2 are as:
{
𝑇1 = (√
3
2
𝑉
𝑠𝛼 −
1
√2
𝑉𝑠𝛽) .
𝑇𝑃𝑊𝑀
𝐸
𝑇2 = √2𝑉𝑠𝛽
𝑇𝑃𝑊𝑀
𝐸
(21)
Figure 5. Principle of space vector modulation Figure 6. Projection of the reference voltage vector
on V1 and V2
The equations for T1 and T2 are identically for all space vector modulation methods.
The only difference between the other types of SVM is the placement of zero vectors at the
sampling time. The basic SVM method is the modulation method with symmetrical spacing zero vectors
(SVPWM). In this method times T0 and T7 are equal [29]:
𝑇0 = 𝑇7 = (𝑇𝑃𝑊𝑀 − 𝑇1 − 𝑇2)/2 (22)
For the first sector switching sequence can be written as:
𝑉0 → 𝑉1 → 𝑉2 → 𝑉7 → 𝑉2 → 𝑉1 → 𝑉0 (23)
6. SIMULATION AND EXPERIMENTAL RESULTS
In order to verify the effectiveness and the performance of the proposed control strategises, both
simulation and experimental tests are carried out. Then a loratory setup was established using dSPACE
system with DS1104 controller board and IGBTs voltage inverter. The electrical parameters of the power
circuit and control data are listed in Table 1.
Table 1. System and control parameters
Prameter Symbol Value
AC line voltage (RMS)
Frequency
Line resistance
Load resistance
AC-side inductance
DC-bus capacitor
DC-bus voltage
e[V]
f[Hz]
R[Ω]
RL[Ω]
L[mH]
C[mF]
VDC[V]
50
50
0.2
64
10
1.1
125
Switching freqency fs[KHz] 10
6.1. Simulation results
Various tests, in simulation stadies, were conducted to verify performance of the proposed VOC
scheme. The results shows the simulated waveforms under unity power factor (UPF) operation (iq,ref=0) in the
stady state for purely sinusoidal supply voltage source. Figures 7 (a)-(e) shows the dynamic behavior under a

1593
step change of VDC,ref , after a short transient, the output voltage is maintained close to its new reference. We
remark that the anti-windup PI DC-bus controller has achived the test goals: no overshoots and better
constancy in steady state. The line currents are very close to sine wave from with a spectral analysis devoid
of low-order harmonics (THD=1.75%) and in phase with the power source voltage because the reactive
current reference component iq,ref was imposed 0A. The reactive current (id) is maintained to zero.
(a) (b)
(c) (d)
(e)
Figure 7. Dynamic response characteristics for step change of the VDC ref, from 125V to 140V and inversely,
using anti-windup PI controller, (a) DC-link voltage, (b) voltage ea and currents phases, (c) zoom on voltage
ea and line currents, (d) dq-currents, (e) harmonic spectrum of line current
To show the good performance of the proposed VOC-SVM control based anti-windup PI controller
during a transient, the load is changed in t1=1s, from 64Ω to 32Ω. It is clearly shown in Figures 8 (a)-(d) that
the system has a good dynamic response to variation load at 1s. The current waveform is perfectely
sinusoidal and has some phase as the voltage waveforms. The reactive current continued zero even with
variation load. With anti-windup PI controller, the output voltage is recouvred in less than 0.05s.
1 1.5 2
120
125
130
135
140
145
time (s)
Vdc(V)
Vdc Vdcref
1 1.5 2
-5
0
5
time (s)
ea/10(V)
and
iabc(A)
1.2 1.22 1.24 1.26
-5
0
5
time (s)
ea/10(V)
and
iabc(A)
1 1.5 2
-2
0
2
4
6
time (s)
id
and
iq(V)
id(V) iq(V)

 ISSN: 2088-8694
1594
(a) (b)
(c) (d)
Figure 8. (a) DC-link voltage, (b)Voltage ea and line currents, (c) zoom on voltage ea and line currents,
(d) dq-currents
6.2. Experimental results
To validate the simulation results of the proposed VOC-SVM with anti-windup PI controller studied
on the above section, different pratical tests were carried out. An experimental test bench is designed by
using a dSPACE 1104 board as illustrated in Figure 9. The dSPACE 1104 board is based on a 250MHz 603-
Power PC-64 bits processor and a slave digital signal processing (DSP) card based on a 20MHz,
TMS320F240-16bits microcontroller used to carry out real-time algorithms. The dSPACE works on
MATLAB/Simulink R2013b platform. The board is equibed with analog-digital converter for voltages and
currents sensors; it’s used with control desk software which makes the record of the results easy.
Figure 9. Different parts of experimental test bench and its dSPACE control
Loking at the experimental results, we can see the dynamic of the VOC-SVM under a step change of
VDCref is presented in Figures 10 (a)-(e), after ashort transient the DC-bus voltage is maintained close to its
0.5 1 1.5
118
120
122
124
126
128
time (s)
Vdc(V)
Vdc(V) Vdcref
0.8 0.9 1 1.1 1.2
-5
0
5
time (s)
ea/10(V)
and
iabc(A)
0.95 1 1.05
-5
0
5
time (s)
ea/10(V)
and
iabc(A)
0.8 0.9 1 1.1 1.2
-2
0
2
4
6
8
time(s)
iq
and
iq
(V)
id(V) iq(V)

1595
new reference with good dynamic, stability and no overshoots. The line current ia shown in Figure 10 (c) is in
phase with the actual power source voltage because the reactive current is controlled to zero, that ensures
unity power factor operation. From the Figure 10 (d), it can be found that the active current control and the
reacrive current control are independent of each other.
The robustness of this control is proven by the exprerimental results of a step response during a
variation of the load (Figures 11 (a)-(e)), the grid currents rmains purely sinusoidal and unaffected by this
load variation. Furthmore, it can be seen that the DC-bus voltage, active current and reactive current remains
regulated at its reference value after a short transient of 50ms. In addition, it is also seen that the active
current undergoes a relative increase in this load variation. The quadrature current iq is kept zero (Figure 11
(d).
(a) (b)
(c) (d)
(e)
Figure 10. Experimental results of, (a) DC-bus voltage, (b) line currents, (c) zoom on voltage and line
currents, (d) dq-currents, (e) duty cycle ratio of SVPWM based on the carrier. Transient response during a
step change of VDCref from 125V to 140V and inversely
10 20 30 40
120
125
130
135
140
145
time (s)
Vdc(V)
Vdc(V) Vdcref(V)
10 20 30 40
-5
0
5
time (s)
iabc(A)
ia ib ic
16.21 16.22 16.23 16.24 16.25
-5
0
5
time (s)
ea(V)
and
iabc(A)
ea ia ib ic
10 20 30 40
-2
0
2
4
6
8
time (s)
idq(A)
currents
id(A) iq(A)
10 10.01 10.02 10.03 10.04 10.05 10.06
0
0.2
0.4
0.6
0.8
1
time (s)
Da Db Dc

 ISSN: 2088-8694
1596
(a) (b)
(c) (d)
Figure 11. Experimental results of (a) DC-bus voltage, (b) line currents, (c) a focused part of voltage and line
currents, (d) dq-curents transient response during a load change, from 64Ω to 86Ω and inversel
7. CONCLUSION
In this paper, simulation and real time implementation study of VOC-SVM control of three phase PWM
rectifier combined with a anti-windup PI controller of DC-bus voltage is presented. For this purpose,
simulation and experimental results shows that the proposed control is able to garantees a good regulation of
the output voltage and give a perfectly sinusoidal line current with a good THD that meets IEEE-519
(THD<2%). In addition, the decoupled feed-forward control strategies ensure a fast-dynamic response and
very good decoupling in active and reactive current control. On the other hand, the proposed VOC scheme
operates with the symetrical SVM that are offering better DC-bus voltage utilization, lower switching loss
and a constant switching frequency.
REFERENCES
[1] J. R. Rodríguez, L. Dixon, JR. Espinoza, J. Pontt, and P. Lezana, “PWM regenerative rectifiers : state of the art,”
IEEE Transactions on Industrial Electronics, vol. 52, no. 1, pp. 5-22, Feb. 2005, doi: 10.1109/TIE.2004.841149.
[2] J. A. A. Caseiro, and A. M. S. Mends, “Performance analysis of three-phase PWM rectifiers for high power quality
applications,” in International Conference on Renewable Energies and Power Quality (ICREPQ’09), Valencia,
Spain. 2009, doi: 10.24084/repqj07.388
[3] J. W. Wilson, “The forced commutated inverter as a regenerative rectifier,” IEEE Transactions on Industry
Applications, vol. IA-14, no. 4, pp. 335-340, July 1978, doi: 10.1109/TIA.1978.4503547.
[4] S. Hansen, M. Malinowski, F. Blaabjerg, and M. P. Kazmierkowski, “Sensorless control strategies for PWM
rectifier,” in APEC 2000. Fifteenth Annual IEEE Applied Power Electronics Conference and Exposition (Cat.
No.00CH37058), 2000, pp. 832-838 vol.2, doi: 10.1109/APEC.2000.822601.
[5] C. J. Zhan, Y. Han, T, Xie, Z. Y. Zhao, and M. C. Wong, “Mathematical model and dual-DSP control of tri-level
PWM reversible rectifier,” in Proceedings of the IEEE 1999 International Conference on Power Electronics and
Drive Systems. PEDS'99 (Cat. No.99TH8475), 1999, pp. 174-179 vol.1, doi: 10.1109/PEDS.1999.794556.
[6] M. P. Kazmierkowski, and L. Malesani, “Current control techniques for three-phase voltage-source PWM
converters: a survey,” IEEE Transactions on Industrial Electronics, vol. 45, no. 5, pp. 691-703, Oct. 1998, doi:
10.1109/41.720325.
[7] Y. Ye, M. Kazerani, and V. H. Quintana, “A novel modeling and control method for three-phase PWM converters,”
in 2001 IEEE 32nd Annual Power Electronics Specialists Conference (IEEE Cat. No.01CH37230), 2001, pp. 102-
107 vol. 1, doi: 10.1109/PESC.2001.954002.
10 20 30 40
110
120
130
140
time (s)
Vdc(V)
Vdcref(V) Vdc(V)
10 15 20 25 30 35
-5
0
5
time (s)
ia ib ic
16.01 16.02 16.03 16.04 16.05 16.06
-5
0
5
10
time (s)
ea/10 ia ib ic
10 20 30 40
-2
0
2
4
6
time (s)
idq(A)
currents
id(A) iq(A)

1597
[8] T. Noguchi, H. Tomiki, and S. Kondo, “Direct power control of PWM converter without power-source voltage
sensor,” IEEE Transactions on Industry Applications, vol. 34, no. 3, pp. 473-479, May-June 1998, doi:
10.1109/28.673716.
[9] A. Bouafia, F. Krim, and J. P. Gaubert, “Fuzzy-logic-based switching state selection for direct power control of
three-phase PWM rectifier,” IEEE Transactions on Industrial Electronics, vol. 56, no. 6, pp. 1984-1992, June 2009,
doi: 10.1109/TIE.2009.2014746.
[10] M. Liserre, A. Dell'Aquila, and F. Blaabjerg, “An overview of three-phase voltage source active rectifiers
interfacing the utility,” in 2003 IEEE Bologna Power Tech Conference Proceedings, 2003, pp. 8 pp. Vol.3, doi:
10.1109/PTC.2003.1304405.
[11] A. M. Razali, and M. A. Rahman, “Performance analysis of three-phase PWM rectifier using direct power control,”
in 2011 IEEE International Electric Machines & Drives Conference (IEMDC), 2011, pp. 1603-1608, doi:
10.1109/IEMDC.2011.5994600.
[12] M. Cichowlas, and M. P. Kamierkowski, “Comparison of current control techniques for PWM rectifiers,” in
Industrial Electronics, 2002. ISIE 2002. Proceedings of the 2002 IEEE International Symposium on, 2002, pp.
1259-1263 vol.4, doi: 10.1109/ISIE.2002.1025970.
[13] M. Malinowski, M. P. Kazmierkowski, and A. Trzynadlowski, “Review and comparative study of control
techniques for three-phase PWM rectifiers,” Mathematics and Computers in Simulation, vol. 63, pp. 349–361,
2003, doi: 10.1016/S0378-4754(03)00081-8.
[14] A. M. Hava, R. J. Kerkman, and T. A. Lipo, “A high performance generalized discontinuous PWM algorithm,” in
Proceedings of APEC 97-Applied Power Electronics Conference, 1997, pp. 886-894 vol. 2, doi:
10.1109/APEC.1997.575750.
[15] W. Jiuhe, Y. Hongren, Z. Jinlong, and Li Huade, “Study on power decoupling control of three phase voltage source
PWM rectifiers,” in 2006 CES/IEEE 5th International Power Electronics and Motion Control Conference, 2006,
pp. 1-5, doi: 10.1109/IPEMC.2006.4778015.
[16] C.T. Pan, and C.T. Chen “Modeling and analysis of a three-phase PWM AC-DC converter without current sensor,”
in IEE Proceedings B (Electric Power Applications), vol. 40, March 1993, doi: 10.1049/ip-b.1993.0024.
[17] J. Lamterkati, M. Khafallah, L. Ouboubker, A. Elafia, and H. Chaikhy, “Implementation of voltage-oriented control
of three-phase PWM rectifier, via Fuzzy and PI controller for output voltage regulation,” Journal Engineering and
applied Sciences JEAS, Medwell Journals, vol. 13, no: 14, pp.5756-5763, september, 2018, doi:
10.36478/jeasci.2018.5756.5763.
[18] M. Malinowski, “Sensorless control strategies for three-phase pwm rectifiers”, Ph.D. dissertation, Faculty of
Electrical Engineering, Institute of Control and Industrial Electronics, Warsaw University of Technology, 2001.
[19] J. F. Mandiola, D.C. Carmona, S. Haghbin, T. Abdulahovic, and M. Ellsen, “An FPGA Implementation of a
Voltage-Oriented Controlled Three-Phase PWM Boost Rectifier,” in 2012 Electrical Systems for Aircraft, Railway
and Ship Propulsion, 2012, pp. 1-6, doi: 10.1109/ESARS.2012.6387430.
[20] B.R. Lin, H.H. Lu, and Y.L. Huo, “Single-phase power factor correction circuit with three-level boost converter,”
in ISIE '99. Proceedings of the IEEE International Symposium on Industrial Electronics (Cat. No.99TH8465),
1999, pp. 445-450 vol.2, doi: 10.1109/ISIE.1999.798653.
[21] P. C. Loh, M. J. Newman, D. N. Zmood, and D. G. Holmes, “Improved transient and steady state voltage regulation
for single and three phase uninterruptible power supplies,” in 2001 IEEE 32nd Annual Power Electronics
Specialists Conference (IEEE Cat. No.01CH37230), 2001, pp. 498-503 vol.2, doi: 10.1109/PESC.2001.954163.
[22] D. Zmood, D. Holmes, and G. Bode, “Frequency-domain analysis of three-phase linear current regulators,” IEEE
Transactions on Industry Applications, vol. 37, no. 2, pp. 601-610, March-April 2001, doi: 10.1109/28.913727.
[23] X.-l. Li, J.-G. Park, and H.-B. Shin, “Comparison and evaluation of anti-Windup PI Controller,” Journal of Power
Electronics, vol. 11, issue. 1, pp. 45-50, 2011, DOI:10.6113/JPE.2011.11.1.045.
[24] S. Ouchen, J. Gaubert, H. Steinhart, and A. Betka, “Energy quality improvement of three-phase shunt active power
filter under different voltage conditions based on predictive direct power control with disturbance rejection
principle,” Mathematics and Computers in Simulation, vol. 159, pp. 506-519, 2019, doi:
10.1016/j.matcom.2018.11.024.
[25] S. Saidi, R. Abbassi, and S. Chebbi, “Virtual fux based direct power control of shunt active filter, “Computer
Science & Engineering and Electrical Engineering, vol. 21, issue. 6, pp. 2165-2176, 2014.
[26] K. Zhou, and D. Wang, “Relationship between space-vector modulation and three-phase carrier-based PWM: a
comprehensive analysis [three-phase inverters],” IEEE Transactions on Industrial Electronics, vol. 49, no. 1, pp.
186-196, Feb. 2002, doi: 10.1109/41.982262.
[27] A. El afia, M. Khafallah, A. Chériti, B. Elmoussaoui, and A Saad, “A Simple Direct Torque Fuzzy Control of
Induction Motor Using Space Vector Modulation,” European Power Electronics and Drives (EPE Journal), vol. 5,
pp. 25-30, 2005, doi: 10.1080/09398368.2005.11463586.
[28] A. Ouarda, and F. Ben Salem, “Induction machine DTC-SVM: A comparison between two approaches,” in 10th
International Multi-Conferences on Systems, Signals & Devices 2013 (SSD13), 2013, pp. 1-7, doi:
10.1109/SSD.2013.6564091.

Implementation on the dSPACE 1104 of VOC-SVM based anti-windup PI Controller of a three-phase PWM rectifier

More Related Content

What's hot (20)

Similar to Implementation on the dSPACE 1104 of VOC-SVM based anti-windup PI Controller of a three-phase PWM rectifier (20)

More from International Journal of Power Electronics and Drive Systems (20)

Recently uploaded (20)

Implementation on the dSPACE 1104 of VOC-SVM based anti-windup PI Controller of a three-phase PWM rectifier